RU2005992C1 - Indication device - Google Patents

Abstract

FIELD: measurement technology. SUBSTANCE: indication device has sweep generator 1, first CRT 2, aerial 3, wide-band amplifier 4, first frequency discriminator 5, first and second differentiation circuits 6 and 7, mixer 8, intermediate frequency amplifier 9, first key 10, first scale-of-eight multiplier 11, first band-pass filter 12, first scale-of-eight divider 13, second band-pass filter 14, first multiplier 15, third band-pass filter 16, second scale-of-eight multiplier 17, fourth band-pass filter 18, second scale-of-eight divider 19, fifth band-pass filter 20, phase detector 21, low-pass filter 22, controlling signal former 23, element 24 of controlled delay, detector 25, delay element 26, second key 27, search unit 28, heterodyne 29, second frequency discriminator 30, phase inverter 31 of 90 deg, reference voltage generator 32, second CRT 33, third CRT 34, second amplitude detector 35, third frequency discriminator 36, third differentiation circuit 37, first single-polarity valve 38, first coincidence element 39, third key 40, second multiplier 41, sixth band-pass filter 42, first amplitude detector 43, first storage 44, first threshold unit 45, fourth key 46, information input 47, reset input 48, third scale-of-eight multiplier 49, first and second meters 50 and 51 of width of spectrum, comparator 52, second threshold unit 53, first analysis unit 54, OR gate 55, phase inverter 56, second single-polarity valve 57, second coincidence element 58, fifth key 59, seventh band-pass filter 60, third amplitude detector 61, second storage 62, third threshold unit 63, sixth key 64, second analysis unit 65, seventh key 66, third analysis unit 67, first, second and third analysis inputs 70,72,74, first and second outputs 71, 73 of analysis unit. EFFECT: expanded range of frequency search of signals without expansion of range of frequency re-tuning of heterodyne. 2 cl, 9 dwg

Description

 The invention relates to indicator and recording devices and can be used for visual analysis and registration of complex signal parameters with combined linear frequency modulation and multiple phase shift keying (LFM-MFMn).

Among the known devices, an indicator device was selected as a prototype, which contains a receiving antenna, a broadband amplifier, a mixer, a local oscillator, an intermediate frequency amplifier, four keys, two frequency multipliers by eight, two frequency dividers by eight, six band-pass filters, three frequency detectors, three cathode ray tubes, two amplitude detectors, three differentiating circuits, a detector, an element will delay, a phase detector, a low-pass filter, a driver of a control signal, an element of a controlled rear Arms, search unit, match element, drive, threshold unit, reference voltage generator and 90 ^o phase shifter.

 The indicator device selected as a prototype provides search, detection in a given frequency range of the LFM-MFMn signals and a visual assessment of their main parameters on the screens of three CRT cathode-ray tubes. In this case, additional (mirror and combination) reception channels are suppressed.

 However, from the point of view of expanding the range of frequency search for signals without expanding the range of frequency tuning of the local oscillator, it is advisable not to suppress additional receiving channels, but to use them.

 The aim of the invention is to expand the range of frequency search for signals without expanding the range of frequency tuning of the local oscillator.

 This goal is achieved by the fact that a seventh bandpass filter, a third amplitude detector, a second drive, a third threshold block, a phase inverter, a second unipolar valve, a second coincidence element, a fifth, sixth, seventh and eighth keys, an OR element, a second, third and the fourth analysis blocks, and the seventh bandpass filter, the third amplitude detector, the second drive, the second input of which is connected to the first outputs of the second and fourth blocks ana, are connected in series to the output of the second multiplier isa, a third threshold block, a sixth key, the second input of which is connected to the output of the third key, and the second analysis unit, a phase meter, a second unipolar valve, a second matching element, the second input of which is connected to the output of the second amplitude detector, are connected in series to the output of the third differentiating circuit, the fifth key, the second input of which is connected to the output of the intermediate frequency amplifier, the seventh key: the second input of which is connected to the output of the threshold block, and the third analysis unit, to the output of the fifth key is the follower but the eighth key is connected, the second input of which is connected to the output of the third threshold block, and the fourth analysis block, the second inputs of the second, third and fourth analysis blocks are connected to the output of the intermediate frequency amplifier, the third inputs are connected to the second output of the search block, and the first inputs of the first, the second, third and fourth analysis blocks through an OR element are connected to the input of the search block, the second outputs of the first and third analysis blocks are connected to the second input of the first drive, the second outputs of the second and fourth block in analysis are connected to a second input of the second reservoir.

 The block diagram of the proposed device is presented in FIG. 1. Structural diagrams of the detector and analysis units are shown in FIG. 2 and 3. A view of the possible waveforms is shown in FIG. 4. Frequency and timing diagrams explaining the operation of the device are shown in FIG. 5, 6, 7, 8 and 9.

The indicator device comprises a sweep generator 1, a first CRT 2, an antenna 3, a broadband amplifier 4, a first frequency detector 5, a first and second differentiating circuits 6 and 7, a mixer 8, an intermediate frequency amplifier 9, a first switch 10, a first eight frequency multiplier, the first band-pass filter 12, the first frequency divider 13 by eight, the second band-pass filter 14, the first multiplier 15, the third band-pass filter 16, the second frequency multiplier 17 by eight, the fourth band-pass filter 18, the second frequency divider 19 by eight, the fifth band-pass filter 20, phase detector 21, low-pass filter 22, control signal driver 23 controlled delay element 24, detector 25, delay element 26, second key 27, search unit 28, local oscillator 29, second frequency detector 30, phase shifter 31 90 ^° , generator 32 voltage references, a second CRT 33, a third CRT 34, a second amplitude detector 35, a third frequency detector 36, a third differentiator circuit 37, a first unipolar valve 38, a first matching element 39, a third key 40, a second multiplier 41, a sixth bandpass filter 42 first amplitude de vector 43, first drive 44, first threshold block 45, fourth key 46, information input 47, reset input 48, third frequency multiplier 49 by eight, first and second spectrum width meters 50 and 51, comparison block 52, second threshold block 53, first analysis unit 54, OR element 55, phase inverter 56, second unipolar valve 57, second matching element 58, fifth key 59, seventh bandpass filter 60, third amplitude detector 61, second drive 62, third threshold block 63, sixth key 64, second analysis block 65, seventh key 66, third analysis block 67, eight my key is 68, the fourth analysis block 69, the first, second and third inputs of the analysis block 70, 72, 74. The first and second outputs 71, 73 of the analysis unit. Moreover, the broadband amplifier 4, mixer 8, the second input of which through the local oscillator 29 is connected to the output of the search unit 28, the intermediate frequency amplifier 9, the frequency detector 36, the differentiating circuit 37, the unipolar valve 38, the coincidence element 39, the second input are connected in series to the output of the antenna 3 which through an amplitude detector 36 is connected to the output of the intermediate frequency amplifier 9, key 40, the second input of which is connected to the output of the intermediate frequency amplifier 9, key 46, the second input of which is connected to the output of the threshold block 45, analyzing unit 54 and an OR gate 55 whose output is connected to the input unit 28 searches. To the output of the broadband amplifier 4, a multiplier 41 is connected in series, the second input of which is connected to the output of the intermediate frequency amplifier 9, a bandpass filter 42, an amplitude detector 43, a drive 44, the second input of which is connected to the second outputs of the analysis blocks 54 and 67, and the threshold block 45. A bandpass filter 60, an amplitude detector 61, a drive 62, the second input of which is connected to the second outputs of the analysis blocks 65 and 69, and a threshold block 63 are connected in series to the output of the multiplier 41. The output of the differentiating circuit 37 is subsequently connected a phase inverter 56, a unipolar valve 57, a coincidence element 58, the second input of which is connected to the output of the amplitude detector 35, the key 59, the second input of which is connected to the output of the intermediate frequency amplifier 9, the key 66, the second input of which is connected to the output of the threshold unit 45, are connected and analysis unit 67. To the output of the key 40, a key 64 is connected in series, the second input of which is connected to the output of the threshold block 63, and the analysis block 65. To the output of the key 59, a key 68 is connected in series, the second input of which is connected to the output of the threshold block 63, and the analysis block 69. The first outputs of blocks 54, 65, 67 and 69 of the analysis are connected through an OR element 55 to the input of block 28 search. The second outputs of blocks 54 and 67 are connected to the second input of the drive 44. The second outputs of blocks 65 and 69 are connected to the second input of the drive 62. The second inputs of these blocks are connected to the outputs of the intermediate frequency amplifier 9, and the third inputs are connected to the second output of the search block 28. The analysis block 54 (65, 67, 69) contains a key 10 connected to the output of the intermediate frequency amplifier 9 (input 70), the second input of which is connected to the output of the detector 25, a frequency multiplier 11, an eight band pass filter, a frequency divider 13, and an eight frequency divider 13 a band-pass filter 14, a frequency detector 5, a differentiating circuit 6, a differentiating circuit 7, a sweep generator 1 and a horizontal CRT electrode 2, the vertical electrode of which is connected to the output of the differentiating circuit 6. An element 24 is connected in series to the output of the band-pass filter 14 delayed delay, multiplier 15, the second input of which is connected to the output of the intermediate frequency amplifier 9 (input 70), bandpass filter 16, frequency multiplier 17 by eight, bandpass filter 18, frequency divider 19 by eight, bandpass filter 20, phase detector 21, second the input of which is connected to the output of the reference voltage generator 32, a low-pass filter 22, and a control signal generator 23, the output of which is connected to the second input of the controlled delay element 24. To the output of the key 46 (64, 66, 68) (input 72), a detector 25 is connected in series, the second input of which is connected through its delay element 26 to its output, and a vertical CRT electrode 33, the horizontal electrode of which is connected to the second output of the search unit 28 (input 74). To the output of the band pass filter 16 connected in series with switch 27, a second input coupled to an output of the detector 25, frequency detector 30 and modulating electrode CRT 34, a vertical electrode which directly and the horizontal electrode through the phase shifter 31 to ⁹⁰ connected to the output of the generator 32 of the reference voltage. The first outputs of the analysis units (output 70) are connected to the second inputs of the drives 44 and 62. The second outputs of these analysis units (output 73) are connected to the OR element 55. The detector 25 is equipped with eight frequency multiplier 39 connected in series to its information input 47, a spectral width meter 51, comparison units 52, the second input of which is connected to an input 47 through a spectral width meter 50, and a threshold block 53 connected via a reset input 48 to the output element 26 delay.

 The device operates as follows.

 Viewing a given frequency range Df is carried out using a search unit 28, which periodically with a saw-tooth period rebuilds the local oscillator frequency 29. At the same time, the search unit 28 forms a horizontal scan of the CRT 33, which is used as the frequency axis and corresponds to the viewing band of the specified frequency range. Keys 10, 27, 40, 46, 59, 64, 66, and 68 are closed in the initial state.

- скорость изменения частоты внутри импульса;
Δf_д - девиация частоты;
φ_к(t) - манипулируемая составляющая фазы, отображающая закон фазовой манипуляции в соответствии с модулирующим кодом М(t) (фиг. 9 а), причем φ_к(t) = const при K τ_э<t<(K+1)τ_э и может изменяться скачком при t = K τ_э, т. е. на границах между элементарными посылками (К = 1, 2 . . . , N - 1);
τ_э, N - длительность и количество элементарных посылок, из которых составлен сигнал длительностью τ_и( τ_и = N τ_э) с выхода приемной антенны 3 через широкополосный усилитель 4 поступает на первый вход смесителя 8, на второй вход которого подается напряжение гетеродина 29 линейно изменяющейся частоты
U_г(t)= V_г˙cos[2 π f_г t+π γ₁ t²+
+φ_г), 0≅t≅T_п, где V_г, f_г, φ_г, T_п - амплитуда, начальная частота, начальная фаза и период повторения напряжения гетеродина;
γ₁=

- скорость изменения частоты гетеродина.Received signal with combined frequency modulation and multiple phase shift keying (LFM-MFMn)
U _c (t) = V _c ˙cos [2 π f _c t + π γ t ² +
+ φ _к (t) + φ _c ], 0≅t≅t _n where V _c , f _c , φ _c , τ _and are the amplitude, initial carrier frequency, initial phase and signal duration;
γ =

- rate of change of frequency inside the pulse;
Δf _d - frequency deviation;
φ _к (t) is the manipulated component of the phase that displays the law of phase manipulation in accordance with the modulating code M (t) (Fig. 9 a), and φ _к (t) = const for K τ _e <t <(K + 1) τ _e and can change abruptly at t = K τ _e , that is, at the boundaries between elementary premises (K = 1, 2 ..., N - 1);
τ _e , N is the duration and number of chips that make up a signal of duration τ _and (τ _and = N τ _e ) from the output of the receiving antenna 3 through the broadband amplifier 4 is fed to the first input of the mixer 8, the second input of which the local oscillator voltage 29 ramp
U _g (t) = V _g ˙cos [2 π f _g t + π γ ₁ t ² +
+ φ _g ), 0≅t≅T _p , where V _g , f _g , φ _g , T _p - amplitude, initial frequency, initial phase and the period of repetition of the local oscillator voltage;
γ ₁ =

- rate of change of the local oscillator frequency.

At the output of mixer 8, the voltages of the Raman frequencies are generated (Fig. 6 a): f _c1 = f _g + γ ₁ tf _c -γ t = f _pr + (γ ₁ -γ) tf _c2 = 2 f _g + γ ₂ tf _c - γ t where the first index denotes the channel through which the signal is received; the second index denotes the harmonic number of the local oscillator frequency involved in the frequency conversion of the received signal:
2f _g is the second harmonic of the local oscillator frequency;
γ ₂ is the rate of change of the second harmonic of the local oscillator frequency (γ ₂ = 2 γ ₁ ).

f_пр, Δf₂ = f_пр.The tuning frequency f _n1 and the passband Δf _{1 of the} intermediate frequency amplifier 9 are selected as follows:
f _H1 = f _etc., Δf ₁ = f 2 _etc.
The tuning frequency f _n2 and the passband Δf _{2 of the} bandpass filter 42 are selected as follows:
f _n2 = f _r +

f _ol , Δf ₂ = f _ol

f_пр, Δf₃ = f_пр
Усилителем 9 выделяется напряжение только промежуточной частоты (фиг. 7 а) U_пр1(t)= V_пр˙cos[2 π f_пр t-φ_к(t)+ +π(γ₁-γ)t₂+φ_пр] , где U_пр=

K₁U_с·U_r; 0 ≅t≅τ_и; К₁ - коэффициент передачи смесителя; f_пр = f_г - f_c - промежуточная частота; φ_пр= φ_г-φ_c - промежуточная начальная фаза.The tuning frequency f _n3 and the passband Δf _{3 of the} bandpass filter 60 are selected as follows:
f _n3 = 2f _r +

f _ol , Δf ₃ = f _ol
Amplifier 9 isolates the voltage of only the intermediate frequency (Fig. 7 a) U _pr1 (t) = V _pr ˙cos [2 π f _pr t-φ _k (t) + π (γ ₁ -γ) t ₂ + φ _pr ] where U _CR =

K ₁ U _s · U _r ; 0 ≅t≅τ _and ; To ₁ - gear ratio of the mixer; f _CR = f _g - f _c - intermediate frequency; φ _CR = φ _g -φ _c - intermediate initial phase.

 This voltage is simultaneously supplied to the second inputs of the multipliers 41 and 15, at the output of the keys 10, 40 and 59, amplitude 35 and frequency 36 detectors. The amplitude detector 35 selects the envelope of the signal (Fig. 7 c), which is fed to the first inputs of the coincidence elements 39 and 58.

From the output of the frequency detector 36, the video signal V ₃₆ (Fig. 7 g), the shape of which corresponds to the law of change of the frequency f _{c1 of the} signal (Fig. 7 b), is input to the differentiating circuit 37, the output voltage (Fig. 7 d) of which is through a unipolar valve 38 (Fig. 7 e) is fed to the second input of the coincidence element 39. Unipolar valves 38 and 57 only allow positive pulses. Since the voltages supplied to the two inputs of the coincidence element 39 occupy the same time interval on the time axis, the coincidence element 39 is activated and opens the key 40 with its output voltage (Fig. 7 g).

 A positive pulse (Fig. 7 d) from the output of the differentiating circuit 37 is simultaneously fed to the input of the bass reflex 56, the output of which is a negative pulse (Fig. 7 h). The specified pulse is passed through a unipolar valve 57.

+φ_г), 0≅t≅τ_и, где U_r1=

K₂U_с·U_пр;
К₂ - коэффициент передачи перемножителя: которое после детектирования в амплитудном детекторе 43 поступает на вход накопителя 44, где оно интегрируется, а затем сравнивается с пороговым напряжением V_пор1 в пороговом блоке 45. При этом пороговый уровень V_пор1 выбирается таким, чтобы его не превышали случайные помехи. При превышении порогового уровня V_пор1 в пороговом блоке 45 формируется постоянное напряжение, которое поступает на управляющий вход ключей 46 и 66, открывая их.The voltage U _pr1 (t) from the output of the intermediate frequency amplifier 9 is simultaneously supplied to the second input of the multiplier 41, the first input of which receives the received signal U _c (t) from the output of the broadband amplifier 4. At the output of the multiplier 41, combinational frequency voltages are generated. However, only the total frequency voltage falls into the passband Δf _{2 of the} bandpass filter 42 (Fig. 6 a)
U

+ φ _g ), 0≅t≅τ _and , where U _r1 =

K ₂ U _s · U _ol ;
K ₂ is the transmission coefficient of the multiplier: which, after detection in the amplitude detector 43, is fed to the input of the drive 44, where it is integrated, and then compared with the threshold voltage V _por1 in the threshold block 45. The threshold level V _por1 is chosen so that it does not exceed random interference. When the threshold level V _por1 is exceeded, a constant voltage is generated in the threshold block 45, which is supplied to the control input of the keys 46 and 66, opening them.

In this case, the voltage U _pr1 (t) from the output of the intermediate frequency amplifier 9 through the public keys 40 and 46 is fed to the first input of the analysis unit 54, namely, to the input of the detector 25 (input 72). At the output of a frequency multiplier 49 by eight detectors 25, an oscillation
U ₁ (t) = V _pr cos [16π f _pr t +
+ 8π (γ ₁ -γ) t ² +8 φ _etc.] in which phase shift keying is already available.

), тогда как ширина спектра Δf_cпринимаемого сигнала определяется длительностью τ_э его элементарных посылок (^Δfc⁼

), т. е. ширина спектра Δf₈ восьмой гармоники сигнала в N раз меньше ширины спектра входного сигнала

= N.The width of the spectrum Δf _{8 of the} eighth harmonic of the signal is determined by the duration τ _{and the} signal (Δf ₈ =

), while the width of the spectrum Δf _{c of the} received signal is determined by the duration τ _{e of} its elementary premises ( ^Δf c ⁼

), i.e., the spectrum width Δf _{8 of the} eighth harmonic of the signal is N times smaller than the spectrum width of the input signal

= N.

 Consequently, when the frequency of the LFM-MPSM signal is multiplied by eight, its spectrum “folds” N times. This circumstance makes it possible to detect the LFM-MFMn signal even when its power at the input of the device is less than the power of noise and interference.

The spectral width Δf _{c of the} input signal is measured using a meter 50, and the spectral width Δf _{8 of the} eighth harmonic of the signal is measured using a meter 51. The voltages V and V ₈ are proportional to Δf _c and Δf _8, respectively, from the outputs of the meters 50 and 51 the spectral widths are two inputs of block 52 comparison. Since V >> V ₈ , a positive pulse is generated at the output of the comparison unit 52, which is compared with the threshold voltage U _pore2 in the threshold block 53. The threshold voltage U _{pore2 is} exceeded only when a LFM-MPSK signal is detected. When the threshold level V _pore2 is exceeded, a constant voltage is generated in the threshold block 53, which is supplied through the OR element 55 (output 73) to the control input of the search unit 28, putting it into stop mode, to the input of the delay element 26, to the control inputs of the keys 10 and 27 opening them and to the vertical electrode CRT 33. From this point in time predetermined range Af preview and search chirped MFMn signal ceases at time visual analysis of the main parameters of the detected chirped MFMn signal is determined by the time delay τ ₃ element 26 delay. In this case, a pulse (frequency mark) is generated on the CRT screen 33, the position of which on the horizontal scan uniquely determines the initial carrier frequency f _{c of the} detected LFM-MPSK signal (Fig. 4a).

Upon termination of viewing a predetermined frequency band Df (when stopping the search block 28) the amplifier 9, the intermediate frequency is a voltage (Fig. 9 b) U _np2 (t) = V _ave cos [2π f _ave t + π γ t ² + + φ _k ( t) + φ _CR ], which through the public key 10 enters the input of the frequency multiplier 11 by eight. At the output of the frequency multiplier 11 by eight, a voltage is generated
U ₂ (t) = V _pr cos [16π f _pr t +
+ 8πγt ² +8 φ _pr ], 0≅t≅τ _and , which is allocated by the band-pass filter 12 and fed to the input of the frequency divider 13 by eight. The output of the latter forms a voltage (Fig. 9 c).

U ₃ (t) = V _pr cos [π f _pr t +
+ πγt ² _pr + φ], 0≅t≅τ _and which is a chirp signal to an intermediate frequency and stands bandpass filter 14. This voltage is supplied to the input of the frequency detector 5, the output of which is formed a video pulse (Fig. 9 g), the shape of which corresponds to the law of linear frequency modulation. The specified video pulse from the output of the frequency detector 5 is fed to the input of the differentiating circuit 6, the output pulse (Fig. 9 d) of which is supplied to the vertical electrode of the CRT 2 and to the input of the differentiating circuit 7, which forms short bipolar pulses (Fig. 9 e). In this case, a positive short pulse starts, and a negative short pulse closes the generator 1 sweep. The generated sawtooth voltage (Fig. 9 g) is supplied to the horizontal CRT electrode 2, a rectangular pulse is generated on the screen (Fig. 4 b), the duration of which is proportional to the duration τ _{and the} received LFM-MPSK signal, the amplitude is proportional to the rate of change of the frequency γ inside the pulse, and the area of the waveform is proportional to the frequency deviation Δf _γ (Δ f _γ = γ τ _and ) of the received LFM-MPSK signal.
For a visual assessment of the main parameters of the received signal, a coordinate frequency-time grid is applied to the CRT 2 screen.

(t)= V_δ cos[2 π f_δ t+φ_к(t)+ +φ_δ] , 0≅t≅τ_и где U_δ=

K₂U $\genfrac{}{}{0ex}{}{\text{2}}{\text{п}}$ _р;
f_δ= γ˙τ- частота биений;
φ_δ= 2 π f_пр τ-π γ τ² - начальная фаза биений, которое представляет собой ФМн сигнал на частоте биений. Напряжений U

( t ) выделяется полосовым фильтром 16 и поступает на вход умножителя 17 частоты на восемь, на выходе которого образуется гармоническое колебание
U

(t)= V_δ cos(16 π f_γ t+8 φ_δ),
0≅t≅τ_и Напряжение U

(t) выделяется полосовым фильтром 18 и поступает на вход делителя 19 частоты на восемь, на выходе которого образуется напряжение (фиг. 9 и)
U

(t)= V_δ cos(2 π f_δ t+ φ_δ),
0≅t≅τ_и которое представляет собой гармоническое колебание на частоте биений. Напряжение U

(t) выделяется полосовым фильтром 20 и поступает на первый вход фазового детектора 21, на второй вход которого подается напряжение с выхода генератора 32 опорного напряжения
U₀(t)= V₀ cos(2 π f₀ t+φ₀) , где V₀, f₀, φ₀ - амплитуда, частота и начальная фаза напряжения генератора.The voltage U ₃ (t) (Fig. 9c) from the output of the band-pass filter 14 is simultaneously supplied to the information input of the controlled delay element 24, the output of which is formed by the voltage U ₄ (t) = U ₃ (t-τ) = V _pr cos [2 π f _pr xx (t-τ) + π γ (t-τ) ² + φ _pr ), 0≅t≅τ _and This voltage is applied to the second input of the multiplier 15, the first input of which receives the received UFM-MPSF signal U _pr2 (t) (Fig. 9 b) of intermediate frequency from the output of amplifier 9 of intermediate frequency. At the output of the multiplier 15, a beat voltage is generated (Fig. 9 h). U

(t) = V _δ cos [2 π f _δ t + φ _к (t) + + φ _δ ], 0≅t≅τ _and where U _δ =

K ₂ U $\genfrac{}{}{0ex}{}{\text{2}}{\text{P}}$ _p ;
f _δ = γ˙τ is the beat frequency;
φ _δ = 2 π f _pr τ-π γ τ ² is the initial phase of the beats, which is the PSK signal at the beat frequency. Stress U

(t) is allocated by a band-pass filter 16 and is fed to the input of a frequency multiplier 17 by eight, at the output of which a harmonic oscillation is formed
U

(t) = V _δ cos (16 π f _γ t + 8 φ _δ ),
0≅t≅τ _and Voltage U

(t) is allocated by the band-pass filter 18 and enters the input of the frequency divider 19 by eight, at the output of which a voltage is generated (Fig. 9 and)
U

(t) = V _δ cos (2 π f _δ t + φ _δ ),
0≅t≅τ _and which is a harmonic oscillation at the beat frequency. Voltage U

(t) is allocated by a band-pass filter 20 and fed to the first input of the phase detector 21, the second input of which is supplied with voltage from the output of the reference voltage generator 32
U ₀ (t) = V ₀ cos (2 π f ₀ t + φ ₀ ), where V ₀ , f ₀ , φ ₀ is the amplitude, frequency, and initial phase of the generator voltage.

 If these voltages differ from each other in frequency or phase, then control voltages are generated at the output of the phase detector 21.

(t) (фиг. 9 з) с выхода полосового фильтра 16 через открытый ключ 27 поступает на вход частотного детектора 30, на выходе которого формируется последовательность коротких равнополярных импульсов (фиг. 9 к), временное положение которых соответствует моментам скачкообразного изменения фазы сигнала (фиг. 9 з).Moreover, the amplitude and polarity of this voltage depends on the degree and direction of the deviation of the beat frequency f _δ , on the frequency f _{0 of the} generator 32 of the reference voltage. The control voltage is allocated by the low-pass filter 22 and, with the help of a signal shaper 23, acts on the control input of the controlled delay element 24 by changing the delay value τ so that the equality f _δ = γ τ = f _{0 is} satisfied. To visually assess the magnitude of the phase jumps Δφ and the multiplicity of phase manipulation of the received LFM-MPSK signal, a circular CRT 34 is used. Moreover, the circular scan is formed using the generator 32 of the reference voltage, the frequency of which is maintained equal to the beat frequency f _δ (f ₀ = f _δ ) using a phase-locked loop. Voltage U

(t) (Fig. 9 h) from the output of the band-pass filter 16 through the public key 27 is fed to the input of the frequency detector 30, the output of which is formed by a sequence of short equal-polarity pulses (Fig. 9 k), the temporary position of which corresponds to the moments of the abrupt change in the signal phase ( Fig. 9 h).

Voltage U ₀ (t) output from the reference voltage generator 32 is supplied directly to the vertical electrode, and through a phase shifter 31 for ⁹⁰ - on the horizontal electrode 34 of the CRT to form at its circumferential screen scan. The formed sequence of short bipolar pulses (Fig. 9 k) from the output of the frequency detector 30 enters the modulating electrode of the CRT 34 and modulates its electron beam in brightness. On the screen of the CRT 34, an image is formed in the form of several bright points located on a circle (Fig. 4 c, d, e). The number of points determines the multiplicity m of phase manipulation, and the angular distance between them is equal to the phase jump Δ φ of the received LFM-MPSM signal. In case of frequency inequality (f _δ ≠ f ₀ ), the brightness marks will move around the circle with a difference frequency, and the reliability of the visual estimation of the multiplicity m of phase manipulation and the magnitude of the phase jumps Δ φ of the received LFM-MPSM signal decreases sharply. To eliminate this drawback, a phase-locked loop is used.

The delay time τ _{3 of the} delay element 26 is selected so that it is possible to visually evaluate the main parameters of the received LFM-MPSF signal by observing the oscillograms on the CRT screens 2, 33 and 34. After this time, the voltage from the output of the delay element 26 is supplied to the detector reset inputs 25 and drive 44 and resets their contents to zero values. In this case, the search unit 28 is transferred to the tuning mode, and the keys 10 and 27 are closed, i.e., are transferred to their initial states. From this point in time, viewing the specified frequency range Df and searching for LFM-MPSK signals continues.

 In case of detection of the next LFM-MPSK signal, the device operates in a similar way.

The operation of the device described above corresponds to the case of receiving the LFM-MPSK signal on the main channel at a frequency f _s (Fig. 5). In this case, the parameters of the received LFM-MPSK signal are analyzed using analysis block 54.

где ^Uпр₁ ⁼

^K1^U3^·Ur; f_пр = f₃ - f_г - промежуточная частота; φ_пр1= φ₃-φ_г
попадает в полосу пропускания Δf₁ усилителя 9 промежуточной частоты. Напряжение U_пр3(t) одновременно поступает на входы амплитудного 35 и частотного 36 детекторов. Амплитудный детектор 35 выделяет огибающую напряжения V₃₅ (фиг. 8 а), которая поступает на первые входы элементов 39 и 58 совпадения. С выхода частотного детектора 36 видеоимпульс V₃₆ (фиг. 8 г), форма которого изменяется по закону линейно падающей пилы, поступает на вход дифференцирующей цепи 37, выходной импульс (фиг. 8 д) которой подается на входы однополярного вентиля 38 и фазоинвертора 56. Однополярный вентиль 38 не пропускает указанный импульс. На выходе фазоинвертора 56 образуется положительный импульс (фиг. 8 е), которой через однополярный вентиль 57 (фиг. 8 ж) поступает на второй вход элемента 58 совпадения. Последний срабатывает и своим выходным импульсом (фиг. 8 з) открывает ключ 59.If the LFM-MPSK signal is received on the mirror channel (Fig. 6 b)
U ₃ (t) = V ₃ ˙cos [2 π f ₃ t + π γ t ² +
+ φ _к (t) + φ ₃ ], 0≅t≅τ _and then in mixers 8 it is converted to voltages of the following frequencies: f ₃₁ = f ₃ + γ tf _g -γ _g t = f _pr + (γ-γ ₁ ) t,
f ₃₂ = 2 f _g + γ ₂ tf ₃ -γ t. However, only the intermediate voltage (difference) frequency (Figures 8a.) U _PR3 (t) = V _pr1 ˙cos [2 π f t + φ _{forth in} (t) -
-π (γ ₁ -γ) t ² +

where ^U CR ₁ ⁼

^K 1 ^U 3 ^{· U} r; f _CR = f ₃ - f _g - intermediate frequency; φ _pr1 = φ ₃ -φ _g
falls into the passband Δf _{1 of the} intermediate frequency amplifier 9. The voltage U _pr3 (t) is simultaneously supplied to the inputs of the amplitude 35 and frequency 36 detectors. The amplitude detector 35 selects the envelope of the voltage V ₃₅ (Fig. 8 a), which is supplied to the first inputs of the coincidence elements 39 and 58. From the output of the frequency detector 36, the video pulse V ₃₆ (Fig. 8 g), the shape of which changes according to the law of a linearly falling saw, is fed to the input of the differentiating circuit 37, the output pulse (Fig. 8 d) of which is supplied to the inputs of a unipolar valve 38 and a phase inverter 56. The unipolar valve 38 does not pass the indicated pulse. At the output of the phase inverter 56, a positive pulse is generated (Fig. 8 e), which is fed through the unipolar valve 57 (Fig. 8 g) to the second input of the matching element 58. The latter is triggered and with its output pulse (Fig. 8 h) opens the key 59.

^K2^U3^·Uпр₁,
которое выделяется полосовым фильтром 42 и после детектирования в амплитудном детекторе 43 поступает на вход накопителя 44, а затем на вход порогового блока 45. Сформированное постоянное напряжение с выхода порогового блока 45 поступает на управляющие входы ключей 46 и 66, открывая их.The voltage U _CR3 (e) from the output of the intermediate frequency amplifier 9 is simultaneously supplied to the second input of the multiplier 41, the first input of which receives the received signal U ₃ (t) from the output of the broadband amplifier 4. A voltage is generated at the output of the multiplier 41
U _r2 (t) = V _r2 ˙cos [2 π f _r t + π γ ₁ t + ²
+ φ _g ], 0≅t≅τ _and , where ^U pr ₂ ⁼

^K 2 ^U 3 ^{· U} PR ₁ ,
which is allocated by the band-pass filter 42 and after detection in the amplitude detector 43 is fed to the input of the drive 44, and then to the input of the threshold unit 45. The generated constant voltage from the output of the threshold unit 45 is supplied to the control inputs of the keys 46 and 66, opening them.

The voltage U _CR3 (t) from the output of the intermediate frequency amplifier 9 through the public keys 59 and 66 is fed to the input of the analysis unit 67, where the parameters of the LFM-MPSM signals received via the mirror channel are visually analyzed.

 If the LFM-MPSK signal is received on the first combinational channel (Fig. 6 c).

то в смесителях 8 он преобразуется в напряжения следующих частот: f₁₂= 2 f_г+γ₂ t-f_к1}-γ

f₁₁= f_к1+γ_к1}+γ

_t
Однако только напряжение с частотой f₁₂ попадает в полосу пропускания Δf₁ усилителя 9 промежуточной частоты (фиг. 7 а) U_пр4(t)= V_пр2˙cos[2 π f_пр t+φ_к(t)- -π(γ₂-γ) t²+

где U

=

K₁U_к1-U_r; f_пр = 2f_г - f_K1 - промежуточная частота; φ_пр2= φ_г-φ_к1.U _к1 (t) = V _к1 ˙cos [2 π f _{к1} t + π γ t} 2 ₊
+ φ _r (t) +

then in mixers 8 it is converted to voltages of the following frequencies: f ₁₂ = 2 f _g + γ ₂ tf _{k1} -γ}

f ₁₁ = f _k1 + γ _{k1} + γ}

_t
However, only a voltage with a frequency f ₁₂ Δf falls within the band ₁ bandwidth intermediate frequency amplifier 9 (FIG 7 a.) U _WP4 (t) = V _np2 ˙cos [2 π f t + φ _{forth in} (t) - -π (γ ₂ -γ) t ² +

where u

=

K _{1 k1} U -U _r; f _CR = 2f _g - f _K1 - intermediate frequency; φ _pr2 = φ _g -φ _k1 .

This voltage is simultaneously supplied to the inputs of the amplitude 35 and frequency 36 detector. The amplitude detector 35 selects the envelope of the voltage V ₃₅ (Fig. 7 c), which is supplied to the first inputs of the coincidence elements 39 and 58 from the output of the frequency detector 36, the video pulse V ₃₆ (Fig. 7 g), the shape of which changes according to the law of a linearly increasing saw ( Fig. 7 b), the input pulse of the differential circuit 37, the output pulse (Fig. 7 d), which is fed to the inputs of a unipolar valve 38 and the phase inverter 56. The output pulse of a unipolar valve 38 (Fig. 7 e) is fed to the second input of the element 39 coincidence, the output pulse of which (Fig. 7 g) is supplied to vlyayuschy input key 40, opening it.

=

K₂U_к1U

, которое выделяется полосовым фильтром 60 и после детектирования в амплитудном детекторе 61, интегрирования в накопителе 62 поступает на вход порогового блока 63, на выходе которого образуется постоянное напряжение. Это напряжение поступает на управляющий вход ключей 64 и 68, открывая их. При этом напряжение U_пр4(t) с выхода усилителя 9 промежуточной частоты через открытые ключи 40 и 64 поступает на вход блока 65 анализа, где визуально анализируются параметры ЛЧМ-МФМн сигнала, принимаемого по первому комбинационному каналу.The voltage U _prn (t) from the output of the intermediate frequency amplifier 9 is supplied to the second input of the multiplier 41, the first input of which receives the received signal U _k1 (t) from the output of the broadband amplifier 4. The voltage U _g3 (t) V _{g3 is} generated at the output of the multiplier 41 ˙cos (4 π f _g t + π γ ₂ t + + φ _g ), 0≅t≅τ _and where U

=

K ₂ U _k1 U

, which is allocated by the band-pass filter 60 and after detection in the amplitude detector 61, integration in the drive 62 is fed to the input of the threshold block 63, at the output of which a constant voltage is generated. This voltage is supplied to the control input of the keys 64 and 68, opening them. The voltage U _CR4 (t) from the output of the intermediate frequency amplifier 9 through the public keys 40 and 64 is fed to the input of the analysis block 65, where the parameters of the LFM-MPSK signal received via the first combination channel are visually analyzed.

, то в смесителях 8 он преобразуется в напряжения следующих частот: f₂₂= 2f_к2}+γ

f₂₁= f_к2+γ t-f_г-γ₁ t Однако только напряжение с частотой f₂₂ попадает в полосу пропускания усилителя 9 промежуточной частоты (фиг. 8 а) U_пр5(t)= V_пр3˙cos[2 π f_пр t+φ_к(t)- -π(γ₂-γ) τ²+

где U

=

K₁U_к2U_r; f_пр = f_K2 - 2 f_г - промежуточная частота; φ_пр3= φ_к2-φ_г.If the LFM-MPSK signal is received via the second combination channel (Fig. 6 g) U _к2 (t) = V _к2 ˙cos (4 π f _{к2} t + π γ t +} + φ _к (t) +

, then in mixers 8 it is converted to voltages of the following frequencies: f ₂₂ = 2f _{k2} + γ}

f ₂₁ = f _k2 + γ tf _r -γ ₁ t However, only a voltage with a frequency f ₂₂ enters the intermediate frequency bandwidth of the amplifier 9 (FIG. 8 a) U _np5 (t) = V _PR3 ˙cos [2 π f t _ave + φ _to (t) - -π (γ ₂ -γ) τ ² +

where u

=

K ₁ U _k2 U _r ; f _CR = f _K2 - 2 f _g - intermediate frequency; φ _pr3 = φ _k2 -φ _g .

This voltage is supplied to the inputs of the amplitude 35 and frequency 36 detectors. The amplitude detector 35 selects the envelope of the voltage V ₃₅ (Fig. 8 c), which is supplied to the first inputs of the coincidence elements 39 and 58. From the output of the frequency detector 36, the video pulse V ₃₆ (Fig. 8 g), the shape of which changes according to the law of a linearly falling saw (Fig. 8 b), is fed to the input of the differentiating circuit 37, the output pulse (Fig. 8 d) of which is fed to the input of the differentiating valve 38 and phase inverter 56. Unipolar valve 38 does not pass the specified pulse. At the output of the phasemeter 56, a positive pulse is generated (Fig. 8 e), which, through a unipolar valve 57 (Fig. 8 g), is fed to the second input of the coincidence element 58. The latter is triggered and with its output pulse (Fig. 8 h) opens the key 59.

^K2^Uк2^Uпр₃,
которое выделяется полосовым фильтром 60 и после детектирования в амплитудном детекторе 61, интегрирования в накопителе 62 поступает на вход порогового блока 63, на выходе которого образуется постоянное напряжение. Это напряжение поступает на управляющие входы ключей 64 и 68, открывая их. При этом напряжение U_пр5(t) с выхода усилителя 9 промежуточной частоты через открытые ключи 59 и 68 поступают на вход блока 69 анализа, где визуально анализируются параметры ЛЧМ-МФМн сигнала, принимаемого по второму комбинационному каналу.The voltage U _pr5 (t) from the output of the intermediate frequency amplifier 9 is fed to the second input of the multiplier 41, the first input of which receives the received signal U _K2 (t) from the output of the broadband amplifier 4. At the output of the multiplier 41, the voltage U _r4 (t) = V _rH ˙cos˙ (4 π f _r t + π γ ₂ t ² + + φ _r), 0≅t≅τ _and where ^U r ₄ ⁼

^K 2 ^U k2 ^U pr ₃ ,
which is allocated by the band-pass filter 60 and after detection in the amplitude detector 61, integration in the drive 62 is fed to the input of the threshold block 63, the output of which is generated by a constant voltage. This voltage is supplied to the control inputs of the keys 64 and 68, opening them. In this case, the voltage U _pr5 (t) from the output of the intermediate frequency amplifier 9 through public keys 59 and 68 is fed to the input of the analysis unit 69, where the parameters of the LFM-MPSK signal received via the second combination channel are visually analyzed.

Thus, the proposed device in comparison with the prototype provides a four-fold extension of the frequency range of the search for complex signals with combined linear frequency modulation and multiple phase shift keying without expanding the frequency range of the local oscillator. This is achieved by using mirror and Raman channels. (56) Copyright certificate of the USSR
N 1744472, cl. G 01 D 7/10, 1991.

Claims (2)

 1. INDICATOR DEVICE containing a receiving antenna in series, a broadband amplifier, a mixer, the second input of which is connected through the local oscillator to the output of the search unit, an intermediate frequency amplifier, a third frequency detector, a third differentiating circuit, a unipolar valve, a first matching element, the second input of which the second amplitude detector is connected to the output of the intermediate frequency amplifier, the third key, the second input of which is connected to the output of the intermediate frequency amplifier, the fourth key and a first analysis unit, the second input of which is connected to the output of the intermediate frequency amplifier, as well as a second multiplier connected in series to the output of the broadband amplifier, the second input of which is connected to the output of the intermediate frequency amplifier, a sixth bandpass filter, a first amplitude detector, a first drive and a first threshold block the output of which is connected to the second input of the fourth key, characterized in that a seventh bandpass filter, a third amplitude detector, a second drive, a third pore are introduced into it the main unit, phase inverter, the second unipolar valve, the second matching element, the fifth, sixth, seventh and eighth keys, the OR element, the second, third and fourth analysis blocks, and the seventh bandpass filter, the third amplitude detector, and the second drive are connected in series to the output of the second multiplier the second input of which is connected to the first outputs of the second and fourth analysis blocks, the third threshold block, the sixth key, the second input of which is connected to the output of the third key, and the second analysis block, to the output of the third differential a phase inverter, a second unipolar valve, a second matching element, the second input of which is connected to the output of the second amplitude detector, the fifth key, the second input of which is connected to the output of the intermediate frequency amplifier, the seventh key, the second input of which is connected to the output of the first threshold block and the third analysis block, the eighth key is connected in series to the output of the fifth key, the second input of which is connected to the output of the third threshold block, and the fourth analysis block, the second inputs are The horn, third and fourth analysis blocks are connected to the output of the intermediate frequency amplifier, their third inputs are connected to the second input of the search block, and the first inputs of the first, second, third and fourth analysis blocks are connected through the OR element to the input of the search block, the second outputs of the first and third analysis units are connected to the second input of the first drive, the second outputs of the second and fourth analysis units are connected to the second input of the second drive. 2. The device according to claim 1, characterized in that the analysis unit is made in the form of a first key in series with the intermediate frequency amplifier output, the second input of which is connected to the output of the detector, the first frequency multiplier by eight, the first band-pass filter, the first frequency divider by eight , a second band-pass filter, a first frequency detector, a first differentiating circuit, a sweep generator and a horizontal electrode of the first cathode ray tube, a vertical electrode is connected to the output of the first differential of the lasing circuit, to the output of the second bandpass filter, a controlled delay element is connected in series, the first multiplier, the second input of which is connected to the output of the intermediate frequency amplifier, the third bandpass filter, the second frequency multiplier by eight, the fourth bandpass filter, the second divider by eight, the fifth bandpass filter, a phase detector, the second input of which is connected to the output of the reference voltage generator, a low-pass filter and a driver of the control signal, the output of which is connected to the second input of the element a controlled delay, the detector is connected in series to the output of the fourth, sixth, seventh, eighth keys, the second input of which is connected to its output through the delay element, and the vertical electrode of the second cathode ray tube, the horizontal electrode of which is connected to the second output of the search unit, to the output the third bandpass filter, a second key is connected in series, the second input of which is connected to the detector output, a second frequency detector, a modulating electrode of the third cathode ray tube, whose vertical electrode is directly, and the horizontal electrode is connected to the output of the reference voltage generator through a 90 ^° phase shifter.

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