[go: up one dir, main page]

WO2025019387A2 - Commande de convertisseurs isolés haute fréquence sans inertie - Google Patents

Commande de convertisseurs isolés haute fréquence sans inertie Download PDF

Info

Publication number
WO2025019387A2
WO2025019387A2 PCT/US2024/037964 US2024037964W WO2025019387A2 WO 2025019387 A2 WO2025019387 A2 WO 2025019387A2 US 2024037964 W US2024037964 W US 2024037964W WO 2025019387 A2 WO2025019387 A2 WO 2025019387A2
Authority
WO
WIPO (PCT)
Prior art keywords
voltage
bridge
power converter
transformer
output
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Pending
Application number
PCT/US2024/037964
Other languages
English (en)
Other versions
WO2025019387A3 (fr
Inventor
Deepak M. DIVAN
Satish Shamsundar BELKHODE
Joseph Benzaquen SUNE
Aniruddh MARELLAPUDI
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Georgia Tech Research Institute
Georgia Tech Research Corp
Original Assignee
Georgia Tech Research Institute
Georgia Tech Research Corp
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Georgia Tech Research Institute, Georgia Tech Research Corp filed Critical Georgia Tech Research Institute
Publication of WO2025019387A2 publication Critical patent/WO2025019387A2/fr
Publication of WO2025019387A3 publication Critical patent/WO2025019387A3/fr
Pending legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/42—Conversion of DC power input into AC power output without possibility of reversal
    • H02M7/44—Conversion of DC power input into AC power output without possibility of reversal by static converters
    • H02M7/48—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/4807—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode having a high frequency intermediate AC stage
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/42—Conversion of DC power input into AC power output without possibility of reversal
    • H02M7/44—Conversion of DC power input into AC power output without possibility of reversal by static converters
    • H02M7/48—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
    • H02M7/53871—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/42—Conversion of DC power input into AC power output without possibility of reversal
    • H02M7/44—Conversion of DC power input into AC power output without possibility of reversal by static converters
    • H02M7/48—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/539—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency
    • H02M7/5395—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency by pulse-width modulation
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/66—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output with possibility of reversal
    • H02M7/68—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output with possibility of reversal by static converters
    • H02M7/72—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output with possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/79—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output with possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/797—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output with possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only

Definitions

  • the present invention relates generally to systems and methods, and more particularly to systems for transferring energy between a DC source and an AC source.
  • a typical DC-to-AC conversion system comprises a power electronic building block to achieve AC voltage with desired magnitude and frequency.
  • such conversion applications also require an isolation stage to either provide connection of different voltage levels or as a galvanic isolation element to decouple faults.
  • Such a need is conventionally met with a low-frequency bulky transformer connected to the output of the AC stage, as shown in FIG. 1A.
  • the state-of-the-art solution to address the DC/AC conversion without using a bulky 60 Hz transformer involves the utilization of multi-stage power conversion stages with a high- frequency link obtained with a dual active bridge (DAB) DC/DC converter as shown in FIG. IB followed by a conventional DC/AC bridge.
  • DAB converter uses a finite leakage inductor (Llk), with power transfer achieved through the control of phase angle difference between the two high-frequency AC waveforms across Llk. This involves careful consideration of Llk value and closed-loop control over the required phase shift for the desired power transfer.
  • Llk finite leakage inductor
  • the transformer and the zero-voltage switching (ZVS) resonant switch become limiting factors to its scalability.
  • the current-source characteristics of the S4T also require reverse blocking switches, which are realized with Silicon IGBTs, and Silicon Carbide diodes connected in series.
  • the S4T still uses the magnetizing inductance of the transformer as an energy transfer element leading to finite inertia between the DC/AC conversion.
  • a power converter system comprises a DC bridge electrically coupled to a DC power source.
  • the power converter may further comprise an AC bridge.
  • the power converter may further comprise a transformer comprising a primary winding interfacing with the DC bridge and a secondary winding interfacing with the AC bridge.
  • the power converter may also comprise a controller configured to control the AC and DC bridges to convert a DC voltage from the DC power source to an AC voltage at an output of the AC bridge.
  • the controller may be further configured to control the DC bridge to provide an input voltage to the primary winding of the transformer.
  • the input voltage may comprise a positive voltage portion and a negative voltage portion.
  • the controller may be further configured to cause the AC bridge to flip a polarity of the output when the primary winding receives one of a positive voltage portion or the negative voltage portion of the input voltage to maintain a desired polarity at the output of the AC bridge.
  • the output of the AC bridge may comprise an inductive or inductive-capacitive filtering circuit configured to provide a sinusoidal output.
  • the input voltage to the primary winding may be a quasi-square wave.
  • the positive voltage portion may be a positive voltage pulse
  • the negative voltage portion may be a negative voltage pulse.
  • the DC bridge may comprise four single direction switches.
  • the AC bridge may comprise four bidirectional switches.
  • the input voltage to the primary winding may further comprise a zero-voltage portion between the positive voltage portion and the negative voltage portion.
  • the controller may be configured to change a current switch state of the bidirectional switches when the voltage of the secondary winding is in the zero-voltage portion of the input voltage.
  • the AC voltage may be a single-phase AC voltage.
  • the controller may be further configured to generate a gating signal to control the bidirectional switches.
  • the controller may be configured to generate the gating signal, at least in part, by generating an error signal that is a difference between a terminal voltage at the output of the AC bridge and a reference voltage.
  • the controller may be further configured to generate the gating signal, at least in part, by integrating the error signal.
  • the gating signal may be further based, at least in part, on a determination of whether the integrated error signal is positive or negative.
  • the AC bridge may comprise six bidirectional switches.
  • the AC voltage may be a three-phase AC voltage.
  • the controller may be further configured to generate a gating signal to control the bidirectional switches.
  • the controller may be configured to generate the gating signal by performing the following steps: obtaining a reference AC voltage vector, selecting, based on the reference vector, two line-voltage errors, inputting the two selected line-voltage errors to two integrators, selecting, based on outputs of the two integrators, a vector such that both line-voltage errors are minimized, and applying the vector until an output of one of the two integrators becomes less than zero.
  • the transformer may comprise a leakage inductance less than 1% of a magnetizing inductance of the transformer.
  • the transformer may comprise a leakage inductance of less than 0.1% of a magnetizing inductance of the transformer.
  • the AC bridge may further comprise a clamping circuit configured to limit voltage spikes across switches of the AC bridge.
  • the controller may be configured to alter the output of the AC bridge by utilizing pulse width modulation.
  • the pulse width modulation may be sigma-delta modulation.
  • the input voltage may be a square wave.
  • the input voltage may be a quasi-square wave.
  • the AC bridge may not be connected in shunt with an energy storage capacitor.
  • the DC voltage from the DC power source may comprise a first magnitude.
  • the AC voltage at the output of the AC bridge may comprise a second magnitude greater than the first magnitude.
  • the converter may further comprise at least one active damping auxiliary circuit connected in parallel with the AC bridge.
  • the at least one active damping circuit may be configured to damp oscillations that occur due to excitation of parasitic elements of the converter.
  • the at least one damping circuit may comprise a damping resistor in series with a bi-directional switch.
  • the converter may further comprise at least one active damping auxiliary circuit connected in series with the AC bridge.
  • the at least one active damping circuit may be configured to damp oscillations that occur due to excitation of parasitic elements of the converter.
  • the at least one damping circuit may comprise a damping resistor in parallel with a bi-directional switch.
  • FIG. 1A provides a schematic illustrates of a conventional DC to AC power converter system known in the prior art.
  • FIG. IB provides a schematic illustrates of a conventional DC to AC power converter system known in the prior art.
  • FIG. 1C provides a schematic illustrates of a conventional DC to AC power converter system known in the prior art.
  • FIG. 2A provides a schematic illustration of a power source in accordance with various embodiments of the present disclosure.
  • FIG. 2B provides a schematic illustration of a power source in accordance with various embodiments of the present disclosure.
  • FIG. 2C provides a schematic illustration of an exemplary power converter system in accordance with various embodiments of the present disclosure.
  • FIG. 2D provides a schematic illustration of a portion of an exemplary power converter system in accordance with various embodiments of the present disclosure.
  • FIG. 2E provides a graphical illustration of exemplary primary and secondary transformer winding voltages, transformer current, and AC bridge output voltage of an exemplary power converter system in accordance with various embodiments of the present disclosure.
  • FIG. 2F provides a graphical illustration of exemplary voltage output of an exemplary power converter system in accordance with various embodiments of the present disclosure.
  • FIG. 3A provides a schematic illustration of an exemplary power converter system in accordance with various embodiments of the present disclosure.
  • FIG. 3B provides a schematic illustration of a portion of an exemplary power converter system in accordance with various embodiments of the present disclosure.
  • FIG. 3C provides a schematic illustration of a portion of an exemplary power converter system in accordance with various embodiments of the present disclosure.
  • FIG. 4 provides a graphical illustration of exemplary waveforms of single-phase AC converter in accordance with various embodiments of the present disclosure.
  • FIG. 5A provides a schematic illustration of an exemplary power converter system in accordance with various embodiments of the present disclosure.
  • FIG. 5B provides a schematic illustration of a cycle control scheme of an exemplary power converter system in accordance with various embodiments of the present disclosure.
  • FIG. 5C provides a graphical illustration of exemplary waveforms of three-phase AC converter in accordance with various embodiments of the present disclosure.
  • FIG. 6A provides a schematic illustration of an exemplary power converter system in accordance with various embodiments of the present disclosure.
  • FIG. 6B provides a schematic illustration of an exemplary power converter system in accordance with various embodiments of the present disclosure.
  • Ranges can be expressed herein as from “about” or “approximately” one particular value and/or to “about” or “approximately” another particular value. When such a range is expressed, another exemplary embodiment includes from the one particular value and/or to the other particular value.
  • substantially free of something can include both being “at least substantially free” of something, or “at least substantially pure”, and being “completely free” of something, or “completely pure”.
  • FIGS. 1A-1C illustrate exemplary configuration of prior art direct current (DC) to alternating current (AC) converter systems in accordance with various embodiments.
  • An example DC to AC converter system 10 comprises a power electronic building block to achieve AC voltage with desired magnitude and frequency. In most of the scenarios, such conversion applications also require an isolation stage to either provide connection of different voltage levels or as a galvanic isolation element to decouple faults.
  • conventional converter systems comprise a low frequency transformer 16 connected to the output of the finished DC to AC stage 14.
  • Other converter systems 10 as depicted in FIG.
  • IB remove the bulk low- frequency transformer by utilizing a multi-stage power conversion stage with a high-frequency link 18 obtained with a dual active bridge (DAB) DC/DC converter 20 followed by a conventional DC/AC bridge 14.
  • DAB dual active bridge
  • the DAB converter system uses a finite leakage inductor (Lik), with power transfer achieved through the control of phase angle difference between the two high- frequency AC waveforms across Li . This involves careful consideration of Lik value and closed- loop control over the required phase shift for the desired power transfer.
  • Lik finite leakage inductor
  • FIG. 1C use single-stage DC/AC conversion.
  • the DC/AC conversion is achieved with a DC side full bride 14 and AC side cycloconverter 22 separated by high-frequency isolation 18.
  • These systems may utilize fast-switching devices such as Silicon Carbide MOSFETs (SiC-MOSFET) to assist with the conversion.
  • SiC-MOSFET Silicon Carbide MOSFET
  • these systems use a finite leakage inductor.
  • the phase shift operation with the cycloconverter involves a closed-loop control with complex real-time computation as an integral part for accurate power transfer.
  • the conventional systems described above require either a complex control mechanism or comprise additional energy storage elements, that represent 'inertia' and can slow down the overall controllability and dynamic performance of the plant.
  • additional energy storage elements that represent 'inertia' and can slow down the overall controllability and dynamic performance of the plant.
  • cost-sensitive applications such as low-cost energy access portals, solar microinverters, residential electrical vehicle (EV) chargers, etc.
  • the existing approaches have been constrained by the cost and size impact of these storage elements.
  • an exemplary high-frequency inertia-less isolated converter comprises DC 210 and AC 220 bridges and a high-frequency transformer 230.
  • the DC bridge 210 can comprise four single direction switches 212A-D, which can be any switches known in the art, including, but not limited to, MOSFET switches.
  • the AC side bridge 220 can comprise a bidirectional switch-based bridge, comprising four bidirectional switches 222A-D.
  • At the heart of the proposed configuration is a simple and low-cost control of the AC bridge 220 that can simultaneously satisfy the control of DC or low-frequency AC waveforms on the output 240 of the AC bridge while also ensuring no DC or low-frequency flux in the high-frequency transformer windings.
  • the transformer comprises a leakage inductance less than 1%, 0. l%-0.5%, or less than 0.1% of a magnetizing inductance of the at least one transformer.
  • Such ultra-low Llk values can be easily achieved with Coaxial Winding Power Transformers (CWT) or with coaxial cable wound transformers.
  • “high-frequency transformer” refers to a galvanically isolated power transformer typically operated above 10 kHz, and typically between 20-40 kHz depending on the rated current and voltage for the transformer.
  • a clamping circuit 250 as shown in FIG. 2D with locally managed energy dissipation, can be added on the transformer side connection of the AC bridge 220 to avoid any occurrence of overvoltage on the bridges due to any remnant energy in Llk.
  • the configuration provides one of the simplest possible means to achieve high-frequency isolated DC to AC conversion.
  • the typical control of the AC side bridge 220 involves the application of a gating signal in such a manner that it realizes the desired output waveform (e.g., the low- frequency square wave, e.g., about 50-60 Hz) while at the same time ensuring that the transformer does not saturate.
  • This can utilize “flipping logic,” which can be used to ensure that both conditions are simultaneously met. Such operation ensures that the transformer winding is not saturated and operates with essentially zero DC flux over every switching cycle.
  • FIGS. 2A-F shows the circuit schematic and representative waveforms for the proposed IIC, including gating pulses for the DC 210 and AC 220 side bridge switches for both positive and negative output voltage generation.
  • an intentional overlap duration can be introduced in the DC 210 and AC 220 side bridges to protect the switches against overvoltage peaks.
  • an intentional short-duration (1-2% of Tsw) zerostate is introduced in the DC 210 and AC 220 bridges during the positive (negative) to negative (positive) voltage level change (yielding quasi- square-wave operation).
  • This overlap duration ensures safe commutation of output current Io in the AC side switches 222A-D.
  • the introduced zero-state allows zero-voltage soft-switching for the AC bridge switches 222A-D, where these switches can be switched with zero voltage.
  • the overlap duration also helps to drain the current in Llk towards zero before it reverses its polarity in the second half of the switching cycle (Tsw).
  • the representative waveforms for such an operation are depicted in Fig. 2F.
  • the output voltage control of the abovediscussed IIC can be achieved by utilizing a discrete pulse modulation control strategy, such as sigma-delta modulation, but integrated with the flipping logic to eliminate transformer core saturation.
  • a discrete pulse modulation control strategy such as sigma-delta modulation
  • the utilization of discrete pulse control enables the delivery of an integral number of discrete pulses to the output, such that fine control of the output voltage spectral components is realized.
  • the discrete pulse modulation control acts on the instantaneous error between the reference and terminal voltage across the AC bridge 220 before connecting to any passive element.
  • This terminal voltage at the AC bridge output 240 can either be sensed or obtained using the previously applied switching states in the controller itself.
  • the integrated error output can be passed to the AC bridge in the form of switching states to reduce the error.
  • the flipping logic can impress the right polarity on the output while ensuring that DC flux is not present. It can also eliminate issues of partial pulses from PWM operation, causing a low-frequency flux in the transformer.
  • the DC bridge 210 can be controlled to act as a simple quasi-square wave (comprising a positive voltage portion, a negative voltage portion, and a zero-voltage portion therebetween) or square wave generator, as discussed earlier. However, their combination basically led to achieving controlled output voltage with bidirectional power transfer capability of the IIC using simpler control and net zero DC flux across the high-frequency transformer. This can ensure an open-loop inertia-less power transfer.
  • FIG. 3A shows a typical circuit schematic for the IIC realizing DC to single-phase controlled AC conversion with the LC filtering stage 255 comprising Lf and Cf providing AC sinusoidal output.
  • the AC bridge 220 of the IIC can directly connect to the AC side through an inductive element without any intermediate passive element or energy storage element.
  • the earlier discussed overlap with short- duration zero states in DC 210 and AC 220 side bridges ensures safe commutation of output current Io even with the presence of an inductive element on the output of the AC bridge 220. Nonetheless, an additional clamping circuit 250 (See FIGS. 2D & 3C) on the output side of the AC bridge 220 can be added to provide an additional layer of protection against any missing overlap event.
  • FIG. 3C An exemplary control scheme block diagram for the DC to single-phase controlled AC using the sigma-delta modulation is shown in FIG. 3C for the single -phase bridge shown in FIG. 3A.
  • the input signals v re f and v a b are two real-time analog signals which involve the reference output voltage and the AC bridge 220 output voltage signals. These signals provide an error signal.
  • the error signal is then applied to an integrator, whose output is then applied to the AC bridge switches 222A-D through the earlier discussed flipping logic. In this way, the error between the reference voltage and the output voltage can be minimized in real-time with net zero flux across the high-frequency transformer 230 over the switching cycle.
  • the gating signals for the AC bridge 220 can be synchronized with the high-frequency link zero crossings to ensure discrete pulses on the output side.
  • this disclosure presents a two integral-based discrete pulse modulation for the three-phase bridge shown in FIG. 5A.
  • the three-phase configuration comprises an LCL filtering stage 510 with Lf, Cf, and Lf passive filtering elements.
  • a block diagram of an exemplary control scheme is shown in FIG. 5B.
  • One of the main objectives for the presented control scheme is to ensure that, unlike in the three integral-based system, both integrators correct the error in real-time at all instants. This is achieved using an 'error selector' logic, which selects two-line voltage errors based on the location of the reference vector.
  • the space vector plane is divided into six sectors (I to VI) defined by the line voltage error vectors (eab, ebc, eca, eba, ecb, and eac).
  • the error selector block applies errors e a b and e to the integrator input.
  • the outputs of these integrators are utilized to select a suitable vector among VI, V2, V6, and VO or V7 such that both errors are converged. If both integrator outputs are greater than zero, vector V 1 will be selected to minimize both errors. In this scenario, vector V 1 will be applied till the moment any of the integrator outputs changes becomes less than zero.
  • the suitable vector is selected at each instant, which minimizes the corresponding errors. In this way, at each instant, both the error integrators are operational to minimize the errors without saturation.
  • the selected vectors are applied with the earlier discussed flipping logic to ensure the application of a similar waveform as that of the DC side across the AC side transformer terminals modified by the turns ratio, achieving the simple, low-cost, inertia-less operation with essentially zero DC flux over every switching cycle.
  • FIG. 5C The representative waveforms for the operation of the DC to three-phase AC IIC are shown in FIG. 5C. As can be seen, both the integrator outputs are driving the input errors toward zero. Further, depending on the position of the reference vector, suitable error vectors are selected by the error selector logic to be applied to the integrator inputs. Finally, the vector selection is carried out, and suitable switching states are selected with the flipping logic by considering the status of the transformer's secondary side voltage. The obtained three-phase voltages are free from any distortion, which is achieved by acting on each of the integrators simultaneously in real-time. In this manner, with just two integrators and without utilizing any transformation, three-phase AC voltage is obtained by maintaining zero phase shift. This provides an inertia-less operation of the converter.
  • Hardware embodiments of the IIC can expose a plethora of parasitic components associated with the HF transformer (HFT), switching devices, magnetics, power board traces/planes, terminations, and wiring, among others. More specifically, the transformer leakage inductance and the equivalent lumped capacitance of the DC and AC bridges are of special interest, as they tend to dominate the high-frequency oscillations (above hundreds of kHz) that occur throughout specific switching transitions. An example of such oscillations for an IIC switching cell, shown in FIG. 2C, is demonstrated in FIG. 6C. In this particular switching transition, the DC bridge is shorting the LV-side of the HFT, and all the bidirectional switches of the AC bridge are triggered ON.
  • HFT HF transformer
  • the IIC can be equipped with an active damping auxiliary circuit 260, as displayed in FIGS. 6A-B.
  • an additional bidirectional switch (S d ) with a damping resistor R d e.g., 100-150 Ohm
  • R d e.g. 100-150 Ohm
  • the switch can be only activated for a small period of time ( ⁇ lus) to insert R d in the circuit and damp the oscillations.
  • S d can be operated with a variable duty cycle to insert a controlled equivalent resistance into the circuit.
  • FIG. 6C show the performance of the active damping circuit and its capability to reduce parasitics-related oscillations when implemented in its series configuration. For such implementation, the peak voltage and current values can be drastically reduced when the damping is activated.

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)
  • Inverter Devices (AREA)

Abstract

Systèmes et procédés de commande de système de convertisseur de puissance. Le système comprend un pont CC couplé électriquement à une source d'alimentation CC. Le système comprend en outre un pont CA. Le système comprend en outre un transformateur comprenant un enroulement primaire en interface avec le pont CC et un enroulement secondaire en interface avec le pont CA. Le système comprend également un dispositif de commande configuré pour commander les ponts CA et CC afin de convertir une tension CC provenant de la source d'alimentation CC en une tension CA au niveau d'une sortie du pont CA. Le dispositif de commande est configuré pour commander le pont CC afin de fournir une tension d'entrée à l'enroulement primaire du transformateur. La tension d'entrée comprend une partie de tension positive et une partie de tension négative. Le dispositif de commande amène le pont CA à inverser une polarité de la sortie.
PCT/US2024/037964 2023-07-14 2024-07-14 Commande de convertisseurs isolés haute fréquence sans inertie Pending WO2025019387A2 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
US202363526796P 2023-07-14 2023-07-14
US63/526,796 2023-07-14

Publications (2)

Publication Number Publication Date
WO2025019387A2 true WO2025019387A2 (fr) 2025-01-23
WO2025019387A3 WO2025019387A3 (fr) 2025-04-17

Family

ID=94282598

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/US2024/037964 Pending WO2025019387A2 (fr) 2023-07-14 2024-07-14 Commande de convertisseurs isolés haute fréquence sans inertie

Country Status (1)

Country Link
WO (1) WO2025019387A2 (fr)

Family Cites Families (8)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP3174189B1 (fr) * 2014-07-24 2020-09-16 NTN Corporation Dispositif de transmission de puissance
US10263508B2 (en) * 2015-07-21 2019-04-16 Christopher Donovan Davidson Single stage isolated AC/DC power factor corrected converter
EP3484040A1 (fr) * 2017-11-09 2019-05-15 CE+T Power Luxembourg SA Onduleur à pont avant ca et topologie cc/cc améliorée
EP3518402B1 (fr) * 2018-01-24 2020-08-05 FRIWO Gerätebau GmbH Convertisseur de puissance résonant et procédé de redémarrage d'un redresseur de sortie d'un convertisseur de puissance résonant
JP6994177B2 (ja) * 2020-03-24 2022-01-14 株式会社安川電機 モータ制御装置、エレベータ駆動システム、及びモータ制御方法
US12255524B2 (en) * 2021-06-30 2025-03-18 Enphase Energy, Inc. Isolated gate driver for bidirectional FET pair
CN113572366A (zh) * 2021-09-10 2021-10-29 伊顿智能动力有限公司 多向有源桥变换器及其控制方法以及功率变换装置
JP7376548B2 (ja) * 2021-10-14 2023-11-08 本田技研工業株式会社 電力変換装置、電力変換装置の制御方法、およびプログラム

Also Published As

Publication number Publication date
WO2025019387A3 (fr) 2025-04-17

Similar Documents

Publication Publication Date Title
CN102301576B (zh) 直流/直流转换器和交流/直流转换器
Divan et al. Zero-switching-loss inverters for high-power applications
US8891261B2 (en) Three-phase three-level soft-switched PFC rectifiers
US6507503B2 (en) Apparatus and a method for voltage conversion
Norrga Experimental study of a soft-switched isolated bidirectional AC–DC converter without auxiliary circuit
US11496044B2 (en) DC/DC converter and neutral-point voltage balance control method thereof
Li et al. A three-phase soft-transition inverter with a novel control strategy for zero-current and near zero-voltage switching
Iyer et al. A high-frequency AC-link single-stage asymmetrical multilevel converter for grid integration of renewable energy systems
US20140254223A1 (en) Method and system for a high speed soft-switching resonant converter
US6026006A (en) Integrated three-phase power converter and method of operation thereof
US5946208A (en) Power converter
WO2012063573A1 (fr) Circuit de filtrage, et appareil de conversion de puissance bidirectionnelle pourvu de ce circuit de filtrage
Almardy et al. Three-phase (LC)(L)-type series-resonant converter with capacitive output filter
Li et al. Soft-switching three-phase matrix based isolated AC-DC converter for DC distribution system
Okutani et al. Analysis and comparison of series resonant converter with embedded filters for high power density DCX of solid-state transformer
Belkhode et al. Single-stage bidirectional inertia-less isolated dc/ac converter
Shi et al. Soft switching PWM cascaded three-level combined DC–DC converters with reduced filter size and wide ZVS load range
Bhattacharya et al. A novel re-configurable llc converter for electric aircraft
Ramirez et al. Details and implementation of a SiC-based solid state transformer prototype
CN114448285A (zh) 三相单级隔离双向ac-dc变换器拓扑结构及其控制方法
WO2025019387A2 (fr) Commande de convertisseurs isolés haute fréquence sans inertie
CN207184352U (zh) 一种交流‑直流变换电路
Alfaris et al. A current-fed quasi Z-source inverter with SiC power modules for EV/HEV applications
WO2019213673A1 (fr) Redresseur du type à matrice buck avec commutateur de survolteur, et son fonctionnement pendant une perte monophasée
Bilakanti et al. Single stage soft-switching tri-port converter for integrating renewable source and storage with grid through galvanic isolation

Legal Events

Date Code Title Description
121 Ep: the epo has been informed by wipo that ep was designated in this application

Ref document number: 24843793

Country of ref document: EP

Kind code of ref document: A2