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WO2019078127A1 - Circuit d'éclairage et outil de lampe de véhicule - Google Patents

Circuit d'éclairage et outil de lampe de véhicule Download PDF

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Publication number
WO2019078127A1
WO2019078127A1 PCT/JP2018/038176 JP2018038176W WO2019078127A1 WO 2019078127 A1 WO2019078127 A1 WO 2019078127A1 JP 2018038176 W JP2018038176 W JP 2018038176W WO 2019078127 A1 WO2019078127 A1 WO 2019078127A1
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WO
WIPO (PCT)
Prior art keywords
converter
voltage
lighting circuit
burst
output
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Ceased
Application number
PCT/JP2018/038176
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English (en)
Japanese (ja)
Inventor
知幸 市川
賢 菊池
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Koito Manufacturing Co Ltd
Original Assignee
Koito Manufacturing Co Ltd
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Koito Manufacturing Co Ltd filed Critical Koito Manufacturing Co Ltd
Priority to JP2019549250A priority Critical patent/JPWO2019078127A1/ja
Priority to CN201880067425.0A priority patent/CN111316548B/zh
Publication of WO2019078127A1 publication Critical patent/WO2019078127A1/fr
Anticipated expiration legal-status Critical
Ceased legal-status Critical Current

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    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B47/00—Circuit arrangements for operating light sources in general, i.e. where the type of light source is not relevant
    • H05B47/10—Controlling the light source
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
    • H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
    • H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/37—Converter circuits
    • H05B45/3725—Switched mode power supply [SMPS]
    • H05B45/38—Switched mode power supply [SMPS] using boost topology

Definitions

  • the present invention relates to a lighting circuit of a light source.
  • Vehicle lamps are generally capable of switching between low beam and high beam.
  • the low beam illuminates the near side with a predetermined illuminance, and a light distribution rule is defined so as not to give glare to oncoming vehicles and preceding vehicles, and is mainly used when traveling in a city area.
  • the high beam illuminates a wide range and a distance ahead with relatively high illuminance, and is mainly used when traveling at high speed on a road where there are few oncoming vehicles and preceding vehicles. Therefore, although the high beam is more excellent in visibility by the driver than the low beam, there is a problem that glare is given to the driver of the vehicle existing in front of the vehicle and the pedestrian.
  • ADB Adaptive Driving Beam: light distribution variable headlamp
  • FIG. 1 is a circuit diagram of a vehicular lamp.
  • the vehicular lamp 100R includes a light source 110 and a lighting circuit 200 thereof.
  • the lighting circuit 200 uses the battery voltage V BAT supplied from the battery 2 as a power supply, and supplies the light source 110 with a driving current according to the target luminance.
  • the light source 110 includes a plurality of light emitting units 112 connected in series. Assuming that the forward voltage per stage of the light emitting unit 112 is Vf and the number of steps of the light emitting unit is N, the output voltage (load voltage) V LOAD of the lighting circuit 200 is V LOAD > Vf ⁇ N Must be satisfied.
  • the topology of lighting circuit 200 is selected based on the relationship between battery voltage V BAT and output voltage V LOAD .
  • N the maximum value of V LOAD is lower than the battery voltage V BAT , so the lighting circuit 200 can be configured with a step-down converter.
  • lighting circuit 200 must be configured with a boost converter or a combination of a boost converter and a buck converter.
  • the lighting circuit 200R includes a boost converter 210 at a front stage, a step-down converter 220 at a rear stage, and controllers 230 and 240 thereof.
  • the output voltage V OUT1 of the step-up converter 210 is stabilized at the target voltage V OUT1 (REF) , and this target voltage is defined so as to satisfy V OUT1 (REF) > Vf ⁇ N.
  • Controller 230 performs constant voltage control on boost converter 210 such that output voltage V OUT1 approaches target value V OUT1 (REF) .
  • the downstream step-down converter 220 receives the stabilized voltage V OUT1 as an input voltage, and supplies a drive current I DRV to the light source 110. Controller 240 performs constant current control of step-down converter 220 such that drive current I DRV approaches a target value.
  • V OUT1 (REF) Vf (MAX) ⁇ N (1)
  • bypass control may be performed in order to turn on / off the individual light emitting units 112 independently, and a bypass switch SW is provided in parallel with each light emitting unit 112.
  • a bypass switch SW When a certain bypass switch SW is turned on, the current flowing to the light emitting unit 112 in parallel with it is diverted to the bypass switch SW so that it is turned off.
  • the bypass control causes the load voltage V LOAD across the light source 110 to dynamically fluctuate.
  • V LOAD Vf ⁇ n It is.
  • V OUT1 (REF) 60 V.
  • the present invention has been made in view of such problems, and one of the exemplary objects of an aspect thereof is to provide a converter that can be miniaturized.
  • the lighting circuit includes a boost converter, and a step-down converter that receives an output voltage of the boost converter and supplies a drive current to a light source.
  • the boost converter operates in a burst mode (intermittent mode) in which an operation period (operation state) and a stop period (stop state) are repeated according to the state of the step-down converter.
  • the output voltage of the upstream step-up converter is adjusted such that the relationship between the input voltage and the output voltage of the downstream step-down converter becomes appropriate, so that the range of step-down ratio of the step-down converter can be limited.
  • the boost converter may enter an operating period when the potential difference between the input and output of the buck converter decreases to the first threshold.
  • the step-up converter may enter the stop period when the potential difference between the input and output of the step-down converter reaches a second threshold higher than the first threshold.
  • the operation period of the boost converter may be defined by a timer. That is, after entering an operation period, when a certain time passes, it may transition to a stop period.
  • the lighting circuit further includes a voltage detection circuit that generates a detection signal according to the potential difference between the input and output of the step-down converter, and a hysteresis comparator that compares the detection signal with a threshold and generates a burst signal according to the comparison result. You may have.
  • the boost converter may be controlled in response to the burst signal.
  • the lighting circuit compares the detection signal with a predetermined threshold value according to the comparison result, and a voltage detection circuit that generates a detection signal in which the potential difference between the input and output of the step-down converter is multiplied by a coefficient switchable by two values. And a comparator that generates a burst signal.
  • the coefficients change in response to the burst signal, and the boost converter may be controlled in response to the burst signal.
  • the vehicular lamp includes a light source and any of the lighting circuits described above.
  • the size of the converter can be reduced.
  • FIG. 1 is a circuit diagram of a vehicle lamp according to a first embodiment.
  • FIG. 6 is an operation waveform diagram of a lighting circuit.
  • FIG. 6 is an operation waveform diagram of a lighting circuit. It is a circuit diagram of a part of lighting circuit concerning one example.
  • It is a circuit diagram of a burst controller concerning one example.
  • FIGS. 7A to 7C are circuit diagrams showing configuration examples of the voltage detection circuit.
  • FIGS. 9A and 9B are circuit diagrams showing configuration examples of the burst controller.
  • FIGS. 10A and 10B are circuit diagrams showing configuration examples of the boost converter and the converter controller.
  • FIG. 13 is an operation waveform diagram of the burst controller of FIG. 12;
  • FIG. 16 is a circuit diagram of a boost converter and a converter controller according to a fourth modification.
  • the state in which the member A is connected to the member B means that the members A and B are electrically connected in addition to the case where the members A and B are physically and directly connected. It also includes the case of indirect connection via other members that do not substantially affect the connection state of the connection or do not impair the function or effect provided by the connection.
  • a state where the member C is provided between the member A and the member B means that the member A and the member C, or the member B and the member C are directly connected, and It also includes the case of indirect connection via other members that do not substantially affect the connection state of the connection or do not impair the function or effect provided by the connection.
  • reference numerals attached to electric signals such as voltage signals and current signals or circuit elements such as resistors and capacitors indicate respective voltage values, current values, or resistance values and capacitance values as necessary. It shall represent.
  • FIG. 2 is a circuit diagram of the vehicular lamp 100 according to the first embodiment.
  • the entire lamp system 1 is shown in FIG.
  • the vehicular lamp 100 includes a light source 110 and a lighting circuit 200.
  • the light source 110 includes a plurality of light emitting units 112_1 to 112_N connected in series.
  • the light emitting unit 112 is, for example, an LED, and the light source 110 is also referred to as an LED bar or an LED string.
  • the light emitting unit 112 may be an LD (laser diode) or an organic EL (Electro Luminescence) element.
  • the plurality of light emitting units 112_1 to 112_N respectively illuminate different regions on the virtual vertical screen in front of the vehicle through an optical system (not shown).
  • the lighting circuit 200 supplies the drive current I DRV to the light source 110 to cause it to emit light.
  • the lighting circuit 200 may have a function of individually turning on and off the plurality of light emitting units 112 (bypass control).
  • the lighting circuit 200 receives a control command SPTN instructing a light distribution pattern from a processor (ECU: Electronic Control Unit) (not shown), and turns on and off the plurality of light emitting units 112 according to the control command SPTN. You may control.
  • ECU Electronic Control Unit
  • the lighting circuit 200 includes a boost converter 210, a step-down converter 220, a converter controller 230, a converter controller 240, a burst controller 250, and a lamp ECU 270.
  • the lamp ECU 270 includes a main switch 272 and a processor 274.
  • the processor 274 is communicable with the vehicle ECU 4 and controls on / off of the main switch 272 based on control commands and information from the vehicle ECU 4 or the converter controller 230, so that an appropriate light distribution pattern can be obtained.
  • Control 240 is communicable with the vehicle ECU 4 and controls on / off of the main switch 272 based on control commands and information from the vehicle ECU 4 or the converter controller 230, so that an appropriate light distribution pattern can be obtained.
  • Boost converter 210 When main switch 272 is turned on, battery voltage V BAT is supplied to boost converter 210.
  • Boost converter 210 a switching operation on the basis of the control pulses S 1 to the converter controller 230 generates, and generates an output voltage V OUT1 boosts the battery voltage V BAT.
  • Converter controller 230 is in the operating state of the boost converter 210, up converter 210, to provide a greater power than the power required by the subsequent step-down converter 220 and the light source 110, which generates control pulses S 1.
  • converter controller 230 feeds back the duty ratio of control pulse S 1 by feedback such that output voltage V OUT1 approaches a prescribed target value V OUT1 (REF) sufficiently higher than assumed load voltage V LOAD. You may adjust it. Or the duty ratio of the control pulse S 1 may be fixed to a certain value.
  • the step-down converter 220 steps down the output voltage V OUT1 to supply the drive current I DRV to the light source 110.
  • Converter controller 240 in one embodiment, the drive current I DRV generates a control pulse S 2 so as to approach the target value I REF, the buck converter 220 may be feedback-controlled (constant current control). Converter controller 240 may use known techniques.
  • Boost converter 210 operates in a burst mode in which an operation period and a stop period are repeated according to the state of step-down converter 220.
  • Converter controller 230 switches boost converter 210 when burst signal S BURST is on level (eg, high), and stops switching of boost converter 210 when burst signal S BURST is off level (eg, low). .
  • burst controller 250 sets burst signal S BURST to the on level, and sets boost converter 210 to the operating state.
  • burst controller 250 sets burst signal S BURST to the off level, and boost converter 210 Is set to stop.
  • FIG. 3 is an operation waveform diagram of the lighting circuit 200. As shown in FIG. First, in order to facilitate understanding, the case where the load voltage V LOAD is constant will be described.
  • the output power of the boost converter 210 is larger than the input power of the step-down converter 220 in the subsequent stage in the on period T ON in which the burst signal S BURST is at a high level. Therefore, the output voltage V OUT1 rises with time. At time t 1, the potential difference ⁇ V reaches the second threshold value V TH2, the output voltage V OUT1 other words reaches V LOAD + V TH2, the burst signal S BURST goes low, enters the OFF period T OFF.
  • the control pulse S 1 is stopped, the switching operation of the boost converter 210 is stopped, the output voltage V OUT1 is lowered with time.
  • time t 2 the the potential difference ⁇ V is decreased to a first threshold value V TH1, the output voltage V OUT1 other words decreases to V LOAD + V TH1, the burst signal S BURST becomes high level, and returns to the on-period T ON .
  • the step-up converter 210 at the front stage operates in the burst mode in which operation and stop are repeated according to the potential difference between the input and output of the step-down converter 220 at the rear stage.
  • FIG. 4 is an operation waveform diagram of the lighting circuit 200. As shown in FIG. Even when the load voltage V LOAD fluctuates, the operation is similar to FIG. By the step-up operation of boost converter 210, output voltage V.sub.OUT2 follows load voltage V.sub.LOAD .
  • the potential difference ⁇ V between the input and output of the step-down converter 220 can be limited to a predetermined range. That it is possible to prevent that the minimum value of the step-down ratio K 2 of the step-down converter 220 becomes too small, it can be designed small buck converter 220.
  • This effect is useful even in applications where the load voltage V LOAD is constant, but is particularly effective in applications where the load voltage V LOAD fluctuates, for example, an application that performs dimming based on bypass control.
  • FIG. 5 is a circuit diagram of a part of the lighting circuit 200 according to an embodiment.
  • a step-down converter 220, a converter controller 240 and a burst controller 250 are shown.
  • Step-down converter 220 includes a converter unit 222 and a current smoothing filter 224.
  • the converter controller 240 to stabilize the coil current I L of the converter circuit 222 by a so-called ripple control.
  • the coil current I L is detected by the current sense resistor R S.
  • Converter controller 240 turns off the switching transistor M 1 reaches the peak threshold is detected values of the coil current I L, the switching transistor M 1 drops to bottom a certain threshold detected value of the coil current I L Turn on.
  • the current smoothing filter 224 removes the ripple component from the coil current I L and supplies the DC component to the light source 110 as the drive current I DRV .
  • the control method of converter controller 240 is not limited to this, and constant current control using an error amplifier may be performed. In this case, current smoothing filter 224 may be omitted.
  • the burst controller 250 includes a voltage detection circuit 252 and a hysteresis comparator 254.
  • the hysteresis comparator 254 compares the detection signal V S with the threshold value V THH ⁇ V THL that changes with two values, and generates a burst signal S BURST according to the comparison result.
  • the lower threshold V THL defines the first threshold V TH1 of FIGS. 3 and 4, and the upper threshold V THH defines the second threshold V TH2 of FIGS. 3 and 4. .
  • two comparators may be used.
  • Boost converter 210 at the front stage is controlled in accordance with burst signal S BURST .
  • FIG. 6 is a circuit diagram of a burst controller 250 according to one embodiment.
  • the voltage detection circuit 252 can be configured by a differential amplifier including the resistors R 11 to R 14 and the operational amplifier OA 1 .
  • Hysteresis comparator 254 may be configured with resistors R21 ⁇ R23 and the operational amplifier (voltage comparator) OA 2.
  • the potential difference ⁇ V can be detected with high accuracy using the operational amplifier.
  • FIG. 7 (a) to 7 (c) are circuit diagrams showing configuration examples of the voltage detection circuit 252.
  • FIG. The voltage detection circuit 252 of FIG. 7A includes resistors R 51 and R 52 (both having a resistance value of R), and transistors Tr 51 and Tr 52 .
  • V1 represents an input voltage V IN2 and V2 represents a load voltage V LOAD .
  • the transistors Tr 51 and Tr 52 form a current mirror circuit, and a current (V 2 ⁇ V BE ) / R flows through the transistor Tr 51 and the resistor R 51 .
  • an emitter follower circuit including a transistor Tr 53 and a resistor R 53 is added to the configuration of FIG. 7A.
  • V S (V 1 ⁇ V 2) ⁇ R 55 / (R 54 + R 55 )
  • the voltage detection circuit 252 of FIGS. 7A to 7C although the detection accuracy is lower than that using the operational amplifier, the voltage detection range can be expanded.
  • the configuration of FIG. 6 may be difficult to adopt due to the limitation of the input range of the operational amplifier. In this case, the configurations of FIGS. 7 (a) to 7 (c) are effective.
  • FIG. 8 is a circuit diagram of a burst controller 250 according to one embodiment.
  • the burst controller 250 includes a voltage detection circuit 256 and a comparator 258.
  • the voltage detection circuit 256 generates a detection signal V S obtained by multiplying the potential difference ⁇ V at the input and output of the step-down converter 220 by a coefficient (gain) that can be switched by two values.
  • the comparator 258 compares the detection signal V S with a predetermined threshold value V TH and generates a burst signal S BURST according to the comparison result.
  • FIGS. 9A and 9B are circuit diagrams showing configuration examples of the burst controller 250.
  • the voltage detection circuit 256 includes a variable voltage dividing circuit including a variable resistor R 40 and the fixed resistor R 41.
  • the resistance value of the variable resistor R 40 changes in two values in accordance with the comparison result (S BURST ).
  • S BURST comparison result
  • the comparator 258 compares the detection signal V S with the threshold value V TH .
  • FIG. 9 (b) shows a specific configuration example of the burst controller 250 of FIG. 9 (a).
  • the resistor R 40 includes resistors R 42 and R 43 and a transistor Tr 43 . When the transistor Tr 43 is off, the resistance of the resistor R 40 is equal to R 42, and when the transistor Tr 43 is on, the resistance of the resistor R 40 is a parallel connection of the resistors R 42 and R 43 .
  • the transistor Tr 41 is a voltage comparison unit.
  • a detection voltage V S which is a voltage drop of the resistor R 40 is applied between the base and the emitter of the transistor Tr 41 .
  • the on / off state of the transistor Tr 41 corresponds to the comparison result of the detection voltage V S and the voltage between the base and the emitter.
  • the on / off state of the transistor Tr 41 is converted into a binary burst signal S BURST by an output stage (inverter) including the transistor Tr 44 .
  • the transistor Tr 42 and the resistors R 45 and R 46 control the on / off of the transistor Tr 43 based on the on / off state of the transistor Tr 41 .
  • the resistor R 40 is a variable resistor
  • the resistor R 41 may be a variable resistor.
  • the transistor Tr 41 is used as the voltage comparison means, the present invention is not limited to this, and a voltage comparator including a differential amplifier may be used.
  • FIGS. 10A and 10B are circuit diagrams showing configuration examples of the boost converter 210 and the converter controller 230.
  • FIG. A converter controller 230 may use a commercially available controller IC.
  • a voltage obtained by adding a margin ⁇ to the maximum value V LOAD (MAX) of the load voltage V LOAD is specified as the target voltage V OUT1 (REF) of the output voltage V OUT1 , and the converter controller 230 performs feedback control of the boost converter 210 It is also good.
  • the feedback control by converter controller 230 functions as a limiter of output voltage V OUT1 .
  • Converter controller 230 has a pulse-by-pulse current limiting function.
  • the output voltage V OUT1 of the boost converter 210 is lower than the target voltage V OUT1 (REF) of feedback control.
  • the pulse-by-pulse current limit Prior to the end of the on time (pulse width) required to keep the output voltage V OUT at V OUT1 (REF) , the pulse-by-pulse current limit is activated.
  • the pulse-by-cycle current limit defines the available power of step-up converter 210, which is designed to exceed the input power of step-down converter 220.
  • the maximum on-duty (maximum on-time) may be limited to define the available power during the operation period.
  • the control pulses S 1 supplied to the gate of the switching transistor M 2 is masked by the burst signal S BURST.
  • the logic gate 232 when the burst signal S BURST indicates the operating state, is passed through the control pulses S 1 to the gate of the switching transistor M 2, when the burst signal S BURST indicates a stop state, the low gate of the switching transistor M 2 Fix to
  • converter controller 230 is provided with an enable (EN) pin.
  • Converter controller 230 is configured to stop the switching operation when a predetermined level (for example, low) is input to the EN pin.
  • a predetermined level for example, low
  • the burst signal S BURST may be input to the EN pin.
  • FIG. 11 is a circuit diagram of a part of the lighting circuit 200 according to the second embodiment. Step-down converter 220 and burst controller 250 are shown in FIG.
  • the operation period of boost converter 210 is defined by a timer.
  • the burst controller 250 includes a voltage detection circuit 260, a comparator 262, and a timer 264.
  • Voltage detection circuit 260 generates detection signal V S according to the potential difference ⁇ V between the input and output of step-down converter 220.
  • the configuration of the voltage detection circuit 260 may be the same as that described above.
  • the comparator 262 compares the voltage detection signal V S with the threshold voltage V THL . Then, it generates a trigger signal TRIG that is asserted (for example, high) when the voltage detection signal V S falls to the threshold value V THL .
  • the timer 264 generates a burst signal S BURST that has a predetermined level for a predetermined time from the assertion of the trigger signal TRIG.
  • FIG. 12 is a circuit diagram of a burst controller 250 according to an embodiment.
  • the voltage detection circuit 260 includes resistors R 90 and R 91 , and is configured in the same manner as the voltage detection circuit 256 of FIG. 9A.
  • the voltage detection circuit 260 may be configured in the same manner as the voltage detection circuit 252 shown in FIGS. 6 and 7A to 7C.
  • the comparator 262 includes transistors Tr 91 and Tr 92 and resistors R 92 , R 93 and R 94 , and is configured in the same manner as the comparator 258 in FIG. 9 (b).
  • the comparator 262 may be configured by a voltage comparator.
  • the timer 264 includes a transistor Tr 93 , a capacitor C 91 , and a transistor Tr 94 .
  • the transistor Tr 93 When the trigger signal TRIG becomes high level, the transistor Tr 93 is turned on, the capacitor C 91 is discharged, the capacitor voltage VC 91 becomes zero, and the transistor Tr 94 is turned on.
  • the transistor Tr 93 When the trigger signal TRIG becomes low level, the transistor Tr 93 is turned off, the capacitor C 91 is charged through the resistors R 95 and R 96 , and the capacitor voltage VC 91 rises. As the capacitor voltage V C91 rises, the potential at the connection node of the resistors R 95 and R 96 also rises, and eventually the transistor Tr 94 is turned off.
  • the burst signal S BURST is associated with the on / off state of the transistor Tr 94 , and indicates a stop / low operation when it is high.
  • the off period of the transistor Tr 94 is considered to be the operation period of the boost converter 210.
  • FIG. 13 is an operation waveform diagram of the burst controller 250 of FIG.
  • the timer 264 may be configured by a one-shot multivibrator.
  • step-down converter 220 includes a constant current driver connected in series with light source 110 to stabilize drive current I DRV by the constant current source, and converter controller 240 connects the constant current driver and light source 110 in series. As the load, in which case the voltage across them is the load voltage V LOAD .
  • burst operation of boost converter 210 is controlled based on the potential difference between the input and output of step-down converter 220, but the invention is not limited thereto.
  • burst controller 250 may generate burst signal S BURST so that the step-down ratio of step-down converter 220 does not fall below a predetermined value (within a predetermined range).
  • Modification 3 Although the embodiment has described the fluctuation of the load voltage V LOAD due to the bypass control method, the factor of the fluctuation of the load voltage V LOAD is not particularly limited.
  • FIG. 14 is a circuit diagram of a boost converter and a converter controller according to a fourth modification.
  • PMOS transistor 234 is provided between the gate of the PWM output pin and the switching transistor M 2 of the converter controller 230.
  • the gate of the PMOS transistor 234 is pulled up to the power supply pin through a resistor R 80.
  • the transistor 236 is provided between the gate of the switch 234 and the ground.
  • a resistor R 80 may be provided between the gate and the source (ie, the PWM pin) of the PMOS transistor 234.
  • the drain of the PMOS transistor 234 is connected to the gate of the switching transistor M 2 via a voltage divider circuit including resistors R 81, R 82.
  • the transistor 236 When the burst signal S BURST is high, the transistor 236 is turned on and the gate of the PMOS transistor 234 is low. In this state, when the control pulse S 1 is high, PMOS transistor 234 is turned on, the gate of the switching transistor M 2 also becomes high. When the control pulse S 1 is low, PMOS transistor 234 is turned off to discharge the gate capacitance of the switching transistor M2 through the body diode 238 of the PMOS transistor 234, the switching transistor M 2 is turned on. Thus, while the burst signal S BURST is high, the switching transistor M 2 can be switched according to the control pulse S 1 .
  • 100 vehicle lamp, 110: light source, 112: light emitting unit, 200: lighting circuit, 210: boost converter, 220: step-down converter, 222: converter unit, 224: current smoothing filter, 230, 240: converter controller, 250: Burst controller, 252: voltage detection circuit, 254: hysteresis comparator, 256: voltage detection circuit, 258: comparator, 260: voltage detection circuit, 262: comparator, 264: timer, 270: lamp ECU, 272: main switch, 274: Processor.
  • the present invention relates to a lighting circuit of a light source.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Circuit Arrangement For Electric Light Sources In General (AREA)
  • Dc-Dc Converters (AREA)

Abstract

L'invention concerne un circuit d'éclairage (200) qui fournit de l'énergie électrique à une source de lumière (110). Un convertisseur abaisseur (220) reçoit une tension de sortie Vout1 d'un convertisseur élévateur (210), et fournit un courant d'attaque IDRV à la source de lumière (110). Le convertisseur élévateur (210) fonctionne dans un mode rafale dans lequel une période de fonctionnement et une période d'arrêt sont répétées, en fonction de l'état du convertisseur abaisseur (220).
PCT/JP2018/038176 2017-10-16 2018-10-12 Circuit d'éclairage et outil de lampe de véhicule Ceased WO2019078127A1 (fr)

Priority Applications (2)

Application Number Priority Date Filing Date Title
JP2019549250A JPWO2019078127A1 (ja) 2017-10-16 2018-10-12 点灯回路および車両用灯具
CN201880067425.0A CN111316548B (zh) 2017-10-16 2018-10-12 点灯电路以及车辆用灯具

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JP2017200332 2017-10-16
JP2017-200332 2017-10-16

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WO2019078127A1 true WO2019078127A1 (fr) 2019-04-25

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Cited By (1)

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Publication number Priority date Publication date Assignee Title
US11388793B2 (en) * 2020-07-28 2022-07-12 Ch Lighting Technology Co., Ltd. Dimmable lighting apparatus

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Publication number Priority date Publication date Assignee Title
CN116017806A (zh) * 2022-12-30 2023-04-25 联晶智能电子有限公司 一种车灯控制系统及控制方法

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