[go: up one dir, main page]

WO2018058956A1 - 一种交流电机控制方法、装置及空调器 - Google Patents

一种交流电机控制方法、装置及空调器 Download PDF

Info

Publication number
WO2018058956A1
WO2018058956A1 PCT/CN2017/082516 CN2017082516W WO2018058956A1 WO 2018058956 A1 WO2018058956 A1 WO 2018058956A1 CN 2017082516 W CN2017082516 W CN 2017082516W WO 2018058956 A1 WO2018058956 A1 WO 2018058956A1
Authority
WO
WIPO (PCT)
Prior art keywords
current
pulse signal
driving pulse
point
motor
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Ceased
Application number
PCT/CN2017/082516
Other languages
English (en)
French (fr)
Inventor
李洪涛
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Midea Group Co Ltd
GD Midea Air Conditioning Equipment Co Ltd
Original Assignee
Midea Group Co Ltd
Guangdong Midea Refrigeration Equipment Co Ltd
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Midea Group Co Ltd, Guangdong Midea Refrigeration Equipment Co Ltd filed Critical Midea Group Co Ltd
Publication of WO2018058956A1 publication Critical patent/WO2018058956A1/zh
Anticipated expiration legal-status Critical
Ceased legal-status Critical Current

Links

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P23/00—Arrangements or methods for the control of AC motors characterised by a control method other than vector control
    • H02P23/04—Arrangements or methods for the control of AC motors characterised by a control method other than vector control specially adapted for damping motor oscillations, e.g. for reducing hunting

Definitions

  • the invention relates to the field of motor control, and in particular to a control method and device for an AC motor and an air conditioner.
  • the speed regulation of the AC asynchronous motor currently used can be realized by adjusting the conduction angle of the motor driving power device such as the thyristor, such as the PG speed motor control in the air conditioner field, as shown in Fig. 1, the AC mains signal
  • the zero-crossing detection circuit is input to the MCU, and the MCU output driving pulse drives the operation of the PG motor through the thyristor-based driving circuit, and the PG motor outputs the rotational speed feedback signal to the MCU, and the MCU controls the pulse width of the driving signal relative to the zero-crossing signal. Control the conduction angle of silicon, and then control the AC voltage value of the AC mains loaded on the PG motor to realize the speed regulation of the PG motor.
  • the thyristor Since the thyristor requires a certain current when the thyristor is turned on when the voltage is applied to the G-electrode, and the current-limiting resistor R6 of the 12V terminal that supplies the voltage to the G-pole also has a heat loss, the thyristor G-pole is turned on.
  • the voltage should not be too long. Due to the inductance characteristics of the winding coil inside the motor, the phase of the AC voltage and the AC current signal loaded on the motor are inconsistent. As shown in Figure 2, when the AC voltage is applied to the motor, the phase of the current passing through the motor will lag.
  • the corresponding AC current signal has zero crossing at C1, that is, the two moments are not simultaneous, when the speed of the PG motor is relatively high or the motor
  • the start-up process when the starting point of the pulse width of the driving pulse output by the MCU is close to the voltage zero-crossing signal, the end point of the pulse appears before the corresponding current zero-crossing point, which starts from the starting point of the driving pulse.
  • the thyristor is turned on, but the thyristor is turned off at the current zero crossing point C1. Thereafter, the thyristor is turned off during the entire AC voltage zero-crossing period, while the thyristor is turned on during the normal state.
  • the thyristor begins to conduct when there is a drive pulse, as shown in Figure 2, the first pulse of the motor drive signal
  • the thyristor is turned on, and the voltage is applied to the PG motor corresponding to the effective voltage C2 of the motor input end, and the PG motor
  • the motor starts to run.
  • the current zero-crossing signal reaches the point C1
  • the current can be turned off because the current crosses zero.
  • the thyristor Since the driving pulse is turned off before the time C1, the current zero-crossing signal At the beginning of the entire AC voltage zero-crossing period, the thyristor is in the off state. As shown in the figure, the effective voltage of the effective voltage of the motor input terminal from the C2 to C3 line is zero. Normally, the effective voltage value should always exist. This causes an unexpected shutdown of the thyristor, causing frequent jitters in the motor at start-up or high-speed operation, and does not reach normal speed.
  • the main object of the present invention is to provide a control method, device and air conditioner based on an AC motor control circuit, and aim to solve the problem that the triggering start point of the driving pulse signal in the prior art is earlier than the AC current corresponding to the current AC input voltage period.
  • the motor drive power device is turned off due to the alternating current signal, which causes the AC motor to frequently jitter during startup or high-speed operation and the operation is unstable.
  • the present invention provides a control method based on an AC motor control circuit, and the control method based on the AC motor control circuit includes the following steps:
  • the step of adjusting a trigger starting point of the current driving pulse signal according to the target rotational speed and the real-time rotational speed feedback signal, and controlling an end point of the current driving pulse signal after the alternating current zero-crossing time comprises:
  • Adjusting a trigger starting point of the current driving pulse signal according to the target rotating speed and the real-time speed feedback signal, and the pulse width of the current driving pulse signal is a preset first pulse width value, so that the end point of the current driving pulse signal is The alternating current is after the zero crossing time.
  • the step of adjusting a trigger starting point of the current driving pulse signal according to the target rotational speed and the real-time rotational speed feedback signal, and controlling an end point of the current driving pulse signal after the alternating current zero-crossing time comprises:
  • the pulse width of the current drive pulse signal is controlled as the time difference between the trigger start point and the time of the next voltage zero crossing.
  • the step of adjusting a trigger starting point of the current driving pulse signal according to the target rotational speed and the real-time rotational speed feedback signal, and controlling an end point of the current driving pulse signal after the alternating current zero-crossing time comprises:
  • the triggering start point of the driving pulse signal is earlier than the current zero crossing point corresponding to the current AC input voltage period, and the end point of the driving pulse signal is controlled at the moment of the alternating current zero crossing point.
  • the following steps include:
  • the pulse width of the current drive pulse signal is adjusted such that the end point of the drive pulse signal is after the moment of the AC current zero crossing.
  • the step of adjusting a trigger starting point of the current driving pulse signal according to the target rotational speed and the real-time rotational speed feedback signal, and controlling the end point of the current driving pulse signal after the alternating current zero-crossing time includes:
  • the pulse width of the current driving pulse signal is controlled to be a preset second pulse width when it is determined that the triggering start point of the driving pulse signal is later than the current zero crossing point corresponding to the current AC input voltage period.
  • the triggering start point of the driving pulse signal is earlier than the current zero crossing point corresponding to the current AC input voltage period, and the end point of the driving pulse signal is controlled at the moment of the alternating current zero crossing point.
  • the following steps include:
  • the triggering start point of the driving pulse signal is earlier than the current zero crossing point corresponding to the current AC input voltage period, and the ending point of the driving pulse signal is controlled at the alternating current zero crossing point.
  • the steps after the moment include:
  • the pulse width of the current drive pulse signal is controlled as the time difference between the trigger start point and the time of the next voltage zero crossing.
  • the step of adjusting a trigger starting point of the current driving pulse signal according to the target rotational speed and the real-time rotational speed feedback signal, and controlling the end point of the current driving pulse signal after the alternating current zero-crossing time includes:
  • the present invention further provides a control device based on an AC motor control circuit, and the control device based on the AC motor control circuit includes:
  • a detecting module configured to detect a zero-crossing signal of an input voltage of the AC motor control circuit and a real-time speed feedback signal of the AC motor;
  • control module configured to adjust a trigger starting point of the current driving pulse signal according to the target rotating speed and the real-time speed feedback signal, and control an ending point of the current driving pulse signal after the moment of the alternating current zero-crossing point; wherein the driving The pulse signal drives the AC motor to reach the target speed.
  • control module is further configured to:
  • Adjusting a trigger starting point of the current driving pulse signal according to the target rotating speed and the real-time speed feedback signal, and the pulse width of the current driving pulse signal is a preset first pulse width value, so that the end point of the current driving pulse signal is The alternating current is after the zero crossing time.
  • control module is further configured to:
  • the pulse width of the current drive pulse signal is controlled as the time difference between the trigger start point and the time of the next voltage zero crossing.
  • control module is further configured to:
  • control module is further configured to:
  • the pulse width of the current drive pulse signal is adjusted such that the end point of the drive pulse signal is after the moment of the AC current zero crossing.
  • control module is further configured to:
  • the pulse width of the current driving pulse signal is controlled to be a preset second pulse width when it is determined that the triggering start point of the driving pulse signal is later than the current zero crossing point corresponding to the current AC input voltage period.
  • control module is further configured to:
  • control module is further configured to:
  • the pulse width of the current drive pulse signal is controlled as the time difference between the trigger start point and the time of the next voltage zero crossing.
  • control module is further configured to:
  • the present invention also provides an air conditioner comprising the above-described control device based on an AC motor control circuit.
  • the AC motor control circuit of the invention obtains the target rotational speed of the device, detects the zero-crossing signal of the input voltage of the AC motor control circuit and the rotational speed feedback signal of the AC motor through the relevant circuit, and the MCU in the AC drive circuit is based on the zero-crossing signal and the rotational speed.
  • the feedback signal outputs a driving pulse signal, and adjusts a trigger starting point of the current driving pulse signal according to the target rotating speed and the real-time speed feedback signal output, and controls an end point of the driving pulse signal to be resolved after the alternating current zero-crossing point
  • the motor is driven by the thyristor or the like in the driving circuit when the current zero crossing point occurs.
  • the power device is turned off and causes abnormal speed and jitter of the AC motor to ensure stable and reliable operation of the AC motor.
  • FIG. 1 is a structural diagram of an AC motor control circuit according to the prior art
  • FIG. 2 is a waveform diagram of a control circuit of an alternating current motor according to the prior art
  • FIG. 3 is a schematic flow chart of a first embodiment of a control method based on an AC motor control circuit according to the present invention
  • FIG. 4 is a waveform diagram of an AC motor control circuit according to first and third embodiments of a control method of an AC motor control circuit according to the present invention
  • FIG. 5 is a waveform diagram of an AC motor control circuit according to second and seventh embodiments of a control method of an AC motor control circuit according to the present invention
  • FIG. 6 is a waveform diagram of another AC motor control circuit according to a fourth embodiment of the control method of the AC motor control circuit of the present invention.
  • FIG. 7 is a waveform diagram of an AC motor control circuit according to fifth and sixth embodiments of a control method of an AC motor control circuit according to the present invention.
  • FIG. 8 is a waveform diagram of an AC motor control circuit according to an eighth embodiment of a control method of an AC motor control circuit according to the present invention.
  • FIG. 9 is a schematic diagram of functional modules of a control device based on an AC motor control circuit of the present invention.
  • FIG. 3 is a flow chart of a control method based on an AC motor control circuit in accordance with a first embodiment of the present invention. As shown in FIG. 3, the control method based on the AC motor control circuit of the embodiment of the present invention includes the following steps:
  • step S10 the target rotational speed of the AC motor is obtained.
  • the target speed is generally obtained by the AC motor control circuit from the device in which it is located.
  • the AC motor control circuit is used for driving the motor of the air conditioner, and the air conditioner obtains the current wind speed gear or wind speed level set by the user, and the MCU passes again.
  • the memory retrieves the target speed value corresponding to the wind speed gear position or the wind speed level, so that the current target speed is obtained.
  • Step S20 detecting a zero-crossing signal of an input voltage of the AC motor control circuit and a real-time speed feedback signal of the AC motor;
  • the AC motor control circuit realizes the zero-crossing signal detection of the AC input voltage through the A-part circuit in the figure.
  • the zero-crossing detection is mainly implemented based on the optocoupler IC1, and is input to the P1 port of the MCU after being shaped by the transistor Q1.
  • the AC voltage zero-crossing signal waveform as shown in FIG. 2 is obtained at the P1 port, and the B portion of FIG. 1 detects the AC motor speed feedback signal and is input to the P3 port of the MCU for detection.
  • Step S30 outputting a trigger start point of the current driving pulse signal according to the target rotation speed and the real-time rotation speed feedback signal output, and controlling an end point of the current driving pulse signal after the time of the alternating current zero-crossing point; wherein the driving pulse The signal drives the AC motor to reach a target speed.
  • the MCU obtains the target speed value. If the user sets the air conditioner to the low wind position, the MCU obtains the low wind position of 800 rpm by taking the memory data table, and further according to the time of the zero-crossing signal, the zero-crossing signal.
  • the initial relative time point gives the initial motor drive pulse signal, as shown in Figure 4 at C3, the motor drive pulse signal is combined with the current motor speed feedback signal to adjust the trigger pulse position of the drive pulse signal after the zero-crossing signal. To adjust the speed of the motor to reach the target speed value.
  • the real-time rotational speed feedback signal of the motor drive circuit obtains the current real-time rotational speed, and adjusts the trigger starting point of the current driving pulse signal according to the target rotational speed value, and the trigger starting point of adjusting the current driving pulse signal as shown in the figure is C3.
  • the first zero-crossing signal of the current at the full voltage of the motor is C1, which is later than the first zero-crossing signal 0 of the AC input voltage.
  • the MCU outputs the pulse signal
  • the end point of the output pulse signal is controlled.
  • the end point of the control drive pulse signal in the figure is C4, which is located after C1.
  • the end point C4 of the driving pulse signal is located after the current zero-crossing point C1, it is ensured that when the current of the alternating current motor crosses the zero time C1, there is still a driving pulse signal, which ensures that the thyristor can still be continuously turned on and does not turn off, so that The effective voltage is still loaded on the AC motor, that is, the effective voltage is still loaded at the time of C1 to C5 in the figure, which ensures that the AC motor can be continuously loaded from the trigger starting point C3 of the pulse signal until the end of the AC voltage zero-crossing period.
  • the voltage avoids the prior art in which the AC motor is turned off due to the current zero-crossing point, and the motor drive power device such as the thyristor is turned off, so that the subsequent AC voltage zero-crossing period cannot load the effective voltage, causing the motor speed to be unstable. An anomaly of jitter has occurred.
  • the current signal of the AC motor in the figure is the current signal when the full voltage is loaded thereon, that is, the AC motor is always loaded continuously during the entire period of the AC voltage, usually When the motor speed is maximum, the current signal of the motor also exists in all cycles.
  • the phase difference between the two can be clearly displayed through multiple zero-crossing points. Of course, it can also be displayed by the current signal of the current motor speed. If the motor is not fully loaded, the current signal must be discontinuous. If you want to show the comparison between its zero-crossing point and the zero-crossing of the AC input voltage, it is not convenient to compare.
  • the phase difference between the voltage and current phases is usually different.
  • the voltage and current of the specific type of motor used are different.
  • the time difference parameter of zero point can be easily obtained in the test, generally a range value, and the maximum value of the range value can be taken as the time difference parameter.
  • the MCU drives the pulse signal to drive the AC motor to reach the target speed through the above control, specifically: the MCU outputs the driving pulse signal to the AC motor driving circuit, and the driving circuit converts according to the driving pulse according to the AC input voltage, and is loaded in the AC motor.
  • the power input terminal realizes the normal operation of the motor.
  • the MCU outputs the driving pulse signal through the P2 port.
  • the motor driving circuit is mainly composed of the motor driving power device. As shown in the figure, the thyristor TR1 and the MCU output the driving pulse signal pass through the triode.
  • the Q2 controls the optocoupler IC3, and the optocoupler IC3 triggers the G-stage of the thyristor according to the pulse signal, so that the thyristor is turned on, when the starting point of the control drive pulse signal is at different times in the AC voltage zero-crossing period
  • the conduction angle of the thyristor is different, which results in different AC currents passing through the thyristor from this week. Therefore, the RMS value of the AC voltage applied to the AC motor is different, thereby changing the rotation speed of the motor and further combining the AC motor.
  • the real-time speed feedback signal determines whether the current speed is the same as the target speed. When the speed is different, the target speed is finally reached by changing the conduction angle of the thyristor.
  • the AC motor control circuit detects the zero-speed signal of the input voltage of the AC motor control circuit and the speed feedback signal of the AC motor through the relevant circuit by acquiring the target rotational speed of the device, and the MCU in the AC drive circuit is based on the zero-crossing signal.
  • the speed feedback signal outputs a driving pulse signal, and adjusts a trigger starting point of the current driving pulse signal according to the target speed and the real-time speed feedback signal output, and controls an end point of the driving pulse signal after the alternating current zero-crossing point
  • the driving pulse signal of the AC motor control circuit when the driving pulse signal of the AC motor control circuit is in the above situation, the power device driven by the motor such as the thyristor in the driving circuit occurs when the current zero crossing point occurs.
  • the abnormal problem of unstable speed and jitter caused by the operation of the AC motor is closed, which ensures the smooth and reliable normal operation of the AC motor.
  • the current adjustment is performed according to the target rotation speed and the real-time rotation speed feedback signal.
  • Driving a triggering start point of the pulse signal, and the pulse width of the current driving pulse signal is a preset first pulse width value, so that the end point of the driving pulse signal is after the moment of the alternating current zero crossing point, that is, controlling the current
  • the pulse width of the drive pulse signal is a preset fixed pulse width value.
  • the pulse width of the motor drive pulse signal is a fixed value, as shown in the figure, the trigger start point C3 of the first motor drive pulse signal, and the end point is C4, which is located after the zero crossing point C1 of the AC motor, and its pulse width.
  • the first pulse width value T1 between C3 and C4, the pulse width of the other driving pulse signals is the first pulse width value, and the MCU controls the output pulse width because the pulse width of the driving pulse signal is a fixed first pulse width value.
  • the time is relatively simple, and can further reliably ensure that the motor drive power device of the AC motor control circuit, such as the thyristor, can be continuously turned on after the AC current zero crossing point, thereby ensuring the normal operation of the motor.
  • the first pulse width is The value range is 1 ⁇ T1 ⁇ 8ms.
  • the end point of controlling the driving pulse signal may further subdivide the control.
  • the next voltage zero-crossing point is further acquired, and the pulse width of the current driving pulse signal is controlled to be the trigger starting point. The time difference between the moments of the next voltage zero crossing.
  • the trigger starting point C3 of the first motor driving pulse signal of the specific drawing is located in the current alternating voltage period.
  • the end point of the MCU control motor drive pulse signal is the next voltage zero-crossing point, that is, C5 time, that is, the motor drive pulse signal starts from the trigger start point until the current AC voltage zero-crossing period.
  • the triggering of the driving pulse signal is determined.
  • the end point of the driving pulse signal is controlled after the AC current zero-crossing time; the AC motor is driven to reach the target according to the driving pulse signal Rotating speed.
  • the first zero-crossing signal of the current at the full voltage of the motor is C1, which is later than the first zero-crossing signal 0 of the AC input voltage.
  • the MCU outputs the pulse signal according to the above S30 step, It is judged whether the trigger starting point of the pulse signal is before the time C1, and if it is before, the end point of the control output pulse signal is after the time C1, that is, the trigger starting point of the motor driving pulse signal in the figure is C3, before the time C1, Then, the end point of the control drive pulse signal is C4, which is located after C1.
  • the end point C4 of the driving pulse signal is located after the current zero-crossing point C1, it is ensured that when the current of the alternating current motor crosses the zero time C1, there is still a driving pulse signal, which ensures that the thyristor can still be continuously turned on and does not turn off, so that The effective voltage is still loaded on the AC motor, that is, the effective voltage is still loaded at the time of C1 to C5 in the figure, which ensures that the AC motor can be continuously loaded from the trigger starting point C3 of the pulse signal until the end of the AC voltage zero-crossing period.
  • the voltage avoids the prior art in which the AC motor is turned off due to the current zero-crossing point, and the motor drive power device such as the thyristor is turned off, so that the subsequent AC voltage zero-crossing period cannot load the effective voltage, causing the motor speed to be unstable. An anomaly of jitter has occurred.
  • the triggering of the driving pulse signal is determined.
  • the starting point is earlier than the AC current zero-crossing point corresponding to the AC input voltage period, the AC current zero-crossing point corresponding to the AC input voltage period is obtained;
  • the pulse width of the current drive pulse signal is adjusted such that the end point of the drive pulse signal is after the moment of the AC current zero crossing.
  • the MCU determines that the triggering start time of the driving pulse signal is earlier than the current zero crossing point of the current AC motor, the AC current zero crossing point corresponding to the current AC input voltage period is acquired, and the current adjustment is adjusted.
  • the pulse width of the drive pulse signal that is, the pulse width of its drive pulse signal, can be varied. Since the target speed of the AC motor is different, the triggering start point of the pulse signal will be different when the MCU outputs the driving pulse signal according to the target speed and the real-time speed feedback signal, and the triggering start point time of the driving pulse signal is earlier than the current AC motor.
  • the motor drive power device When the current crosses the zero point, in order to ensure that the motor drive power device can be continuously turned on and not turned off at the time of the zero crossing of the AC motor, it is necessary to control the end point of the driving pulse signal after the moment of the AC current zero crossing. Specifically, as long as the end point is at a fixed time of a small preset time difference after the zero-crossing point of the alternating current, that is, as long as the motor-driven power device can be continuously turned on at the zero-crossing point of the alternating current, The triggering start point of the drive pulse signal is variable, and the end time is fixed, so the pulse width of the drive pulse is variable. Specifically, as shown in FIG.
  • the start point of the trigger of the first drive pulse to the third drive pulse of the motor drive signal is different, and the end point of the pulse is a fixed time, after each current zero-crossing time, therefore
  • the pulse width is different.
  • the triggering starting point of the driving pulse gradually approaches the voltage zero-crossing point in the current week, such as
  • the trigger starting point of the first to third pulses in the figure is gradually closer to the first zero-crossing point of the AC input voltage, so that the pulse width of the driving pulse is gradually longer, and each pulse width is different, that is, the pulse in the figure
  • the processing scheme can ensure that the pulse width of the driving pulse is as narrow as possible when the current driving device of the AC motor is continuously turned on, and the loss current of the power device is further reduced.
  • the driving pulse signal is determined.
  • the pulse width of the current driving pulse signal is controlled to be a preset second pulse width.
  • the MCU determines that the triggering start point of the driving pulse signal is later than the AC current zero-crossing point corresponding to the current AC input voltage period
  • the MCU controls the pulse width of the driving pulse signal to change to the second pulse width, that is,
  • the fixed time value is as shown in FIG. 7 based on the third embodiment.
  • the pulse pulse width is adjusted to a fixed time value, and the pulse is adjusted.
  • the width is a fixed time value T5, or as shown in FIG.
  • the fourth pulse width is also a fixed time value T5, since the triggering start point of the pulse signal is later than the current corresponding to the AC input voltage period.
  • T5 the pulse width of the driving pulse signal
  • the pulse width of the driving pulse signal can be reduced as long as the driving pulse signal can normally trigger the motor driving power device such as the thyristor to be turned on. Pulse width of the pulse signal is reduced, current consumption can be further reduced power device.
  • the first pulse width value ranges from 100 ⁇ T5 ⁇ 800us.
  • the triggering of the driving pulse signal is determined.
  • the pulse width of the current driving pulse signal is controlled to be a preset third pulse width, so that the end point of the driving pulse signal is in the alternating current After the current zero crossing time.
  • the pulse width of the motor driving pulse signal is a preset third pulse width, that is, a preset fixed value, as shown in the figure, the trigger starting point C3 of the first motor driving pulse signal, and the ending point is C4, after the AC motor zero-crossing point C1, its pulse width is the first pulse width value between C3 and C4, and the pulse widths of other driving pulse signals are the third pulse width value T1, because the pulse width of the driving pulse signal is
  • the fixed third pulse width value the MCU controls the output pulse width is relatively simple, and can further reliably ensure that after the AC current zero crossing point, the motor drive power device of the AC motor control circuit such as the thyristor can be continuously turned on, ensuring the motor Normal operation.
  • the first pulse width value ranges from 1 ⁇ T1 ⁇ 8ms.
  • the seventh embodiment of the control method of the AC motor control circuit based on the third embodiment of the control method based on the AC motor control circuit of the present invention, it is determined that the triggering start point of the driving pulse signal is earlier than the current communication.
  • the AC current corresponding to the voltage period corresponds to the zero-crossing point
  • the next voltage zero-crossing point is obtained; the pulse width of the current driving pulse signal is controlled as the time difference between the trigger starting point and the next voltage zero-crossing point.
  • the MCU determines that the trigger starting point of the current driving pulse signal is earlier than the AC current zero-crossing point corresponding to the current AC input voltage period
  • the MCU controls the current driving pulse signal by detecting the next voltage zero-crossing point.
  • the trigger starting point C3 of the first motor drive pulse signal of the specific drawing is located before the AC current zero-crossing point C1 corresponding to the current AC voltage cycle.
  • the end point of the MCU control motor drive pulse signal is A voltage zero-crossing point, that is, C5 moment, that is, the motor driving pulse signal ends from the triggering starting point until the current AC voltage zero-crossing period ends, because the AC current zero-crossing point corresponding to the current AC voltage period is in its voltage zero-crossing period.
  • the motor drive power device of the AC motor control circuit such as the thyristor
  • the effective voltage of the motor input is always loaded during this time.
  • the effective voltage of the motor input terminal always has a waveform between C3 and C5, which ensures the normal operation of the motor.
  • the pulse width of the current driving pulse signal is controlled to be a preset fourth pulse width, and the fourth pulse width is greater than the pulse width of the current pulse signal.
  • the MCU when the MCU determines that the triggering start point of the driving pulse signal is later than the AC current zero-crossing point corresponding to the current AC input voltage period, the MCU controls the pulse width of the driving pulse signal to change to the second pulse width, that is, is fixed.
  • the time value is as shown in FIG. 7 based on the sixth embodiment.
  • the pulse pulse width is adjusted to a fixed time value, and the pulse width thereof. For a fixed time value T5, or as shown in FIG.
  • the fourth pulse width is also a fixed time value T5, since the trigger starting point of the pulse signal is later than the AC current corresponding to the current input voltage period.
  • T5 the pulse width of the driving pulse signal can be reduced, as long as the driving pulse signal can normally trigger the motor driving power device such as the thyristor to be turned on, The pulse width of the pulse signal is reduced, which further reduces the loss current of the power device.
  • the first pulse width value ranges from 100 ⁇ T5 ⁇ 800us.
  • the MCU determines that the triggering start point of the driving pulse signal is earlier than the current zero crossing point corresponding to the current AC input voltage period, corresponding to the first to third driving pulses, and the pulse signal is preset.
  • the third pulse width value T3 when the MCU determines that the triggering start point of the driving pulse signal is later than the alternating current zero crossing point corresponding to the current AC input voltage period, in order to reliably ensure the motor drive of the AC motor control circuit after the AC current zero crossing point If the power device such as the thyristor can be continuously turned on, the preset third pulse width value T3 is greater than T5.
  • the value range of T3 is 1 ⁇ T3 ⁇ 8ms, and the value range of T5 is 100 ⁇ T5 ⁇ 800us. .
  • the pulse width of the current driving pulse signal of the MCU is from the triggering starting point to the next voltage zero-crossing point.
  • the time difference between the current drive pulses is also greater than T5.
  • the present invention also provides a control device based on an AC motor control circuit.
  • FIG. 9 is a schematic diagram of functional modules of a first embodiment of an air conditioner control device based on a wearable device according to the present invention.
  • the wearable device-based air conditioner control device includes:
  • the detecting module 2 is configured to detect a zero-crossing signal of an input voltage of the AC motor control circuit and a real-time speed feedback signal of the AC motor;
  • the control module 3 is configured to adjust a trigger starting point of the current driving pulse signal according to the target rotational speed and the real-time rotational speed feedback signal, and control an end point of the current driving pulse signal after the alternating current zero-crossing point; wherein the driving pulse signal is driven The AC motor runs to the target speed.
  • the target rotational speed is generally obtained by the AC motor control circuit from the device in which it is located.
  • the AC motor control circuit is used for driving the motor of the air conditioner, and the air conditioner obtains the current wind speed gear set by the user, and the MCU then retrieves the storage.
  • the corresponding target speed value is such that the acquisition module 1 acquires the current target speed.
  • the AC motor control circuit realizes the zero-crossing signal detection of the AC input voltage through the A-part circuit in the figure.
  • the zero-crossing detection is mainly implemented based on the optocoupler IC1, and is input to the P1 port of the MCU after being shaped by the transistor Q1.
  • the AC voltage zero-crossing signal waveform as shown in FIG. 2 is obtained at the P1 port, and the B portion of FIG. 1 detects the AC motor speed feedback signal and is input to the P3 port of the MCU for detection.
  • the MCU obtains the target speed value. If the user sets the air conditioner to the low wind position, the MCU obtains the low wind position of 800 rpm by taking the memory data table, and further according to the time of the zero-crossing signal, and then the zero-crossing signal.
  • the initial relative time point gives the initial motor drive pulse signal, as shown in Figure 4 at C3, the motor drive pulse signal is combined with the current motor speed feedback signal to adjust the trigger pulse position of the drive pulse signal after the zero-crossing signal. To adjust the speed of the motor to reach the target speed value.
  • the real-time rotational speed feedback signal of the motor drive circuit obtains the current real-time rotational speed, and adjusts the trigger starting point of the current driving pulse signal according to the target rotational speed value, and the trigger starting point of adjusting the current driving pulse signal as shown in the figure is C3.
  • the first zero-crossing signal of the current at the full voltage of the motor is C1, which is later than the first zero-crossing signal 0 of the AC input voltage.
  • the MCU outputs the pulse signal
  • the end point of the output pulse signal is controlled.
  • the end point of the control drive pulse signal in the figure is C4, which is located after C1.
  • the end point C4 of the driving pulse signal is located after the current zero-crossing point C1, it is ensured that when the current of the alternating current motor crosses the zero time C1, there is still a driving pulse signal, which ensures that the thyristor can still be continuously turned on and does not turn off, so that The effective voltage is still loaded on the AC motor, that is, the effective voltage is still loaded at the time of C1 to C5 in the figure, which ensures that the AC motor can be continuously loaded from the trigger starting point C3 of the pulse signal until the end of the AC voltage zero-crossing period.
  • the voltage avoids the prior art in which the AC motor is turned off due to the current zero-crossing point, and the motor drive power device such as the thyristor is turned off, so that the subsequent AC voltage zero-crossing period cannot load the effective voltage, causing the motor speed to be unstable. An anomaly of jitter has occurred.
  • the current signal of the AC motor in the figure is the current signal when the full voltage is applied thereto, that is, the AC motor is always loaded continuously during the entire period of the voltage, usually the motor. At the maximum speed, the current signal of the motor is also present in all cycles. The phase difference between the two can be clearly displayed through multiple zero-crossing points. Of course, it can also be displayed by the current signal of the current motor speed. If the motor is not fully loaded, the current signal must be discontinuous. If you want to show the comparison between its zero-crossing point and the zero-crossing of the AC input voltage, it is not convenient to compare.
  • the phase difference between the voltage and current phases is usually different.
  • the voltage and current of the specific type of motor used are different.
  • the time difference parameter of zero point can be easily obtained in the test, generally a range value, and the maximum value of the range value can be taken as the time difference parameter.
  • the MCU drives the pulse signal to drive the AC motor to reach the target speed through the above control, specifically: the MCU outputs the driving pulse signal to the AC motor driving circuit, and the driving circuit converts according to the driving pulse according to the AC input voltage, and is loaded in the AC motor.
  • the power input terminal realizes the normal operation of the motor.
  • the MCU outputs the driving pulse signal through the P2 port.
  • the motor driving circuit is mainly composed of the motor driving power device. As shown in the figure, the thyristor TR1 and the MCU output the driving pulse signal pass through the triode.
  • the Q2 controls the optocoupler IC3, and the optocoupler IC3 triggers the G-stage of the thyristor according to the pulse signal, so that the thyristor is turned on, when the starting point of the control drive pulse signal is at different times in the AC voltage zero-crossing period
  • the conduction angle of the thyristor is different, which results in different AC currents passing through the thyristor from this week. Therefore, the RMS value of the AC voltage applied to the AC motor is different, thereby changing the rotation speed of the motor and further combining the AC motor.
  • the real-time speed feedback signal determines whether the current speed is the same as the target speed. When the speed is different, the target speed is finally reached by changing the conduction angle of the thyristor.
  • the AC motor control circuit detects the zero-speed signal of the input voltage of the AC motor control circuit and the speed feedback signal of the AC motor through the relevant circuit by acquiring the target rotational speed of the device, and the MCU in the AC drive circuit is based on the zero-crossing signal.
  • the speed feedback signal outputs a driving pulse signal, and adjusts a trigger starting point of the current driving pulse signal according to the target speed and the real-time speed feedback signal output, and controls an end point of the driving pulse signal after the alternating current zero-crossing point
  • the driving pulse signal of the AC motor control circuit when the driving pulse signal of the AC motor control circuit is in the above situation, the power device driven by the motor such as the thyristor in the driving circuit occurs when the current zero crossing point occurs.
  • the abnormal problem of unstable speed and jitter caused by the operation of the AC motor is closed, which ensures the smooth and reliable normal operation of the AC motor.
  • the current adjustment is performed according to the target rotational speed and the real-time rotational speed feedback signal.
  • Driving a triggering start point of the pulse signal, and the pulse width of the current driving pulse signal is a preset first pulse width value, so that the end point of the driving pulse signal is after the moment of the alternating current zero crossing point, that is, controlling the current
  • the pulse width of the drive pulse signal is a preset fixed pulse width value.
  • the pulse width of the motor drive pulse signal is a fixed value, as shown in the figure, the trigger start point C3 of the first motor drive pulse signal, and the end point is C4, which is located after the zero crossing point C1 of the AC motor, and its pulse width.
  • the first pulse width value T1 between C3 and C4, the pulse width of the other driving pulse signals is the first pulse width value, and the MCU controls the output pulse width because the pulse width of the driving pulse signal is a fixed first pulse width value.
  • the time is relatively simple, and can further reliably ensure that the motor drive power device of the AC motor control circuit, such as the thyristor, can be continuously turned on after the AC current zero crossing point, thereby ensuring the normal operation of the motor.
  • the first pulse width is The value range is 1 ⁇ T1 ⁇ 8ms.
  • the end point of controlling the driving pulse signal may further subdivide the control.
  • the next voltage zero-crossing point is further acquired, and the pulse width of the current driving pulse signal is controlled to be the trigger starting point. The time difference between the moments of the next voltage zero crossing.
  • the trigger starting point C3 of the first motor driving pulse signal of the specific drawing is located in the current alternating voltage period.
  • the end point of the MCU control motor drive pulse signal is the next voltage zero-crossing point, that is, C5 time, that is, the motor drive pulse signal starts from the trigger start point until the current AC voltage zero-crossing period.
  • the triggering of the driving pulse signal is determined.
  • the end point of the driving pulse signal is controlled after the AC current zero-crossing time; the AC motor is driven to reach the target according to the driving pulse signal Rotating speed.
  • the first zero-crossing signal of the current at the full voltage of the motor is C1, which is later than the first zero-crossing signal 0 of the AC input voltage.
  • the MCU outputs the pulse signal according to the above S30 step, It is judged whether the trigger starting point of the pulse signal is before the time C1, and if it is before, the end point of the control output pulse signal is after the time C1, that is, the trigger starting point of the motor driving pulse signal in the figure is C3, before the time C1, Then, the end point of the control drive pulse signal is C4, which is located after C1.
  • the end point C4 of the driving pulse signal is located after the current zero-crossing point C1, it is ensured that when the current of the alternating current motor crosses the zero time C1, there is still a driving pulse signal, which ensures that the thyristor can still be continuously turned on and does not turn off, so that The effective voltage is still loaded on the AC motor, that is, the effective voltage is still loaded at the time of C1 to C5 in the figure, which ensures that the AC motor can be continuously loaded from the trigger starting point C3 of the pulse signal until the end of the AC voltage zero-crossing period.
  • the voltage avoids the prior art in which the AC motor is turned off due to the current zero-crossing point, and the motor drive power device such as the thyristor is turned off, so that the subsequent AC voltage zero-crossing period cannot load the effective voltage, causing the motor speed to be unstable. An anomaly of jitter has occurred.
  • the triggering of the driving pulse signal is determined.
  • the starting point is earlier than the AC current zero-crossing point corresponding to the AC input voltage period, the AC current zero-crossing point corresponding to the AC input voltage period is obtained;
  • the pulse width of the current drive pulse signal is adjusted such that the end point of the drive pulse signal is after the moment of the AC current zero crossing.
  • the MCU determines that the triggering start time of the driving pulse signal is earlier than the current zero crossing point of the current AC motor, the AC current zero crossing point corresponding to the current AC input voltage period is acquired, and the current adjustment is adjusted.
  • the pulse width of the drive pulse signal that is, the pulse width of its drive pulse signal, can be varied. Since the target speed of the AC motor is different, the triggering start point of the pulse signal will be different when the MCU outputs the driving pulse signal according to the target speed and the real-time speed feedback signal, and the triggering start point time of the driving pulse signal is earlier than the current AC motor.
  • the motor drive power device When the current crosses the zero point, in order to ensure that the motor drive power device can be continuously turned on and not turned off at the time of the zero crossing of the AC motor, it is necessary to control the end point of the driving pulse signal after the moment of the AC current zero crossing. Specifically, as long as the end point is at a fixed time of a small preset time difference after the zero-crossing point of the alternating current, that is, as long as the motor-driven power device can be continuously turned on at the zero-crossing point of the alternating current, The triggering start point of the drive pulse signal is variable, and the end time is fixed, so the pulse width of the drive pulse is variable. Specifically, as shown in FIG.
  • the start point of the trigger of the first drive pulse to the third drive pulse of the motor drive signal is different, and the end point of the pulse is a fixed time, after each current zero-crossing time, therefore
  • the pulse width is different.
  • the triggering starting point of the driving pulse gradually approaches the voltage zero-crossing point in the current week, such as
  • the trigger starting point of the first to third pulses in the figure is gradually closer to the first zero-crossing point of the AC input voltage, so that the pulse width of the driving pulse is gradually longer, and each pulse width is different, that is, the pulse in the figure
  • the processing scheme can ensure that the pulse width of the driving pulse is as narrow as possible when the current driving device of the AC motor is continuously turned on, and the loss current of the power device is further reduced.
  • the drive pulse signal is determined.
  • the pulse width of the current driving pulse signal is controlled to be a preset second pulse width.
  • the MCU determines that the triggering start point of the driving pulse signal is later than the AC current zero-crossing point corresponding to the current AC input voltage period
  • the MCU controls the pulse width of the driving pulse signal to change to the second pulse width, that is,
  • the fixed time value is as shown in FIG. 7 based on the third embodiment.
  • the pulse pulse width is adjusted to a fixed time value, and the pulse is adjusted.
  • the width is a fixed time value T5, or as shown in FIG.
  • the fourth pulse width is also a fixed time value T5, since the triggering start point of the pulse signal is later than the current corresponding to the AC input voltage period.
  • T5 the pulse width of the driving pulse signal
  • the pulse width of the driving pulse signal can be reduced as long as the driving pulse signal can normally trigger the motor driving power device such as the thyristor to be turned on. Pulse width of the pulse signal is reduced, current consumption can be further reduced power device.
  • the first pulse width value ranges from 100 ⁇ T5 ⁇ 800us.
  • the triggering of the drive pulse signal is determined.
  • the pulse width of the current driving pulse signal is controlled to be a preset third pulse width, so that the end point of the driving pulse signal is in the alternating current After the current zero crossing time.
  • the pulse width of the motor driving pulse signal is a preset third pulse width, that is, a preset fixed value, as shown in the figure, the trigger starting point C3 of the first motor driving pulse signal, and the ending point is C4, after the AC motor zero-crossing point C1, its pulse width is the first pulse width value between C3 and C4, and the pulse widths of other driving pulse signals are the third pulse width value T1, because the pulse width of the driving pulse signal is
  • the fixed third pulse width value the MCU controls the output pulse width is relatively simple, and can further reliably ensure that after the AC current zero crossing point, the motor drive power device of the AC motor control circuit such as the thyristor can be continuously turned on, ensuring the motor Normal operation.
  • the first pulse width value ranges from 1 ⁇ T1 ⁇ 8ms.
  • the seventh embodiment of the control device for the AC motor control circuit based on the third embodiment of the control device based on the AC motor control circuit of the present invention, it is determined that the triggering start point of the driving pulse signal is earlier than the current communication.
  • the AC current corresponding to the voltage period corresponds to the zero-crossing point
  • the next voltage zero-crossing point is obtained; the pulse width of the current driving pulse signal is controlled as the time difference between the trigger starting point and the next voltage zero-crossing point.
  • the MCU determines that the trigger starting point of the current driving pulse signal is earlier than the AC current zero-crossing point corresponding to the current AC input voltage period
  • the MCU controls the current driving pulse signal by detecting the next voltage zero-crossing point.
  • the trigger starting point C3 of the first motor drive pulse signal of the specific drawing is located before the AC current zero-crossing point C1 corresponding to the current AC voltage cycle.
  • the end point of the MCU control motor drive pulse signal is A voltage zero-crossing point, that is, C5 moment, that is, the motor driving pulse signal ends from the triggering starting point until the current AC voltage zero-crossing period ends, because the AC current zero-crossing point corresponding to the current AC voltage period is in its voltage zero-crossing period.
  • the motor drive power device of the AC motor control circuit such as the thyristor
  • the effective voltage of the motor input is always loaded during this time.
  • the effective voltage of the motor input terminal always has a waveform between C3 and C5, which ensures the normal operation of the motor.
  • the pulse width of the current driving pulse signal is controlled to be a preset fourth pulse width, and the fourth pulse width is greater than the pulse width of the current pulse signal.
  • the MCU when the MCU determines that the triggering start point of the driving pulse signal is later than the AC current zero-crossing point corresponding to the current AC input voltage period, the MCU controls the pulse width of the driving pulse signal to change to the second pulse width, that is, is fixed.
  • the time value is as shown in FIG. 7 based on the sixth embodiment.
  • the pulse pulse width is adjusted to a fixed time value, and the pulse width thereof. For a fixed time value T5, or as shown in FIG.
  • the fourth pulse width is also a fixed time value T5, since the trigger starting point of the pulse signal is later than the AC current corresponding to the current input voltage period.
  • T5 the pulse width of the driving pulse signal can be reduced, as long as the driving pulse signal can normally trigger the motor driving power device such as the thyristor to be turned on, The pulse width of the pulse signal is reduced, which further reduces the loss current of the power device.
  • the first pulse width value ranges from 100 ⁇ T5 ⁇ 800us.
  • the MCU determines that the triggering start point of the driving pulse signal is earlier than the current zero crossing point corresponding to the current AC input voltage period, corresponding to the first to third driving pulses, and the pulse signal is preset.
  • the third pulse width value T3 when the MCU determines that the triggering start point of the driving pulse signal is later than the alternating current zero crossing point corresponding to the current AC input voltage period, in order to reliably ensure the motor drive of the AC motor control circuit after the AC current zero crossing point If the power device such as the thyristor can be continuously turned on, the preset third pulse width value T3 is greater than T5.
  • the value range of T3 is 1 ⁇ T3 ⁇ 8ms, and the value range of T5 is 100 ⁇ T5 ⁇ 800us. .
  • the pulse width of the current driving pulse signal of the MCU is from the triggering starting point to the next voltage zero-crossing point.
  • the time difference between the current drive pulses is also greater than T5.
  • the invention also provides an air conditioner.
  • the air conditioner includes, in addition to the various components and control circuits mentioned in the prior art, the above-mentioned control device based on the AC motor control circuit for controlling the indoor or outdoor fan of the air conditioner. run.
  • the AC motor control circuit of the air conditioner detects the zero-crossing signal of the input voltage of the AC motor control circuit and the speed feedback signal of the AC motor through the relevant circuit by acquiring the target rotational speed of the device, and the AC drive circuit
  • the MCU outputs a driving pulse signal according to the zero-crossing signal and the speed feedback signal, and adjusts a trigger starting point of the current driving pulse signal according to the target speed and the real-time speed feedback signal output, and adjusts the current according to the target speed and the real-time speed feedback signal output.
  • the triggering starting point of the driving pulse signal avoids the controllable driving circuit in the driving circuit when the AC motor control circuit is in the above situation when the AC motor control circuit is in the above situation.
  • the power device driven by a motor such as silicon is turned off, causing an abnormal problem of unstable speed and jitter during operation of the AC motor, ensuring stable and reliable normal operation of the AC motor.

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Motor And Converter Starters (AREA)
  • Control Of Ac Motors In General (AREA)

Abstract

一种基于交流电机控制电路的控制方法、装置及空调器，控制方法包括：获取交流电机的目标转速（S10），并检测交流电机控制电路输入电压的过零信号以及交流电机的实时转速反馈信号（S20），以及根据目标转速和实时转速反馈信号输出驱动脉冲信号，并根据目标转速和实时转速反馈信号输出调整当前驱动脉冲信号的触发起始点，控制驱动脉冲信号的结束点在交流电流过零点时刻之后，最后根据驱动脉冲信号驱动交流电机运行达到目标转速（S30），因此保证交流电机避免出现转速不稳的异常问题，保证了交流电机的平稳可靠运行。

Description

一种交流电机控制方法、装置及空调器
技术领域
本发明涉及电机控制领域，尤其涉及一种交流电机的控制方法、装置及空调器。
背景技术
目前用到的交流异步电机的调速可通过调节电机驱动功率器件如可控硅的导通角的大小实现，如空调器领域的PG调速电机控制，如图1所示，交流市电信号通过过零检测电路输入到MCU，MCU输出驱动脉冲通过基于可控硅的驱动电路驱动PG电机的运转，PG电机输出转速反馈信号到MCU，MCU通过调节驱动信号相对过零信号的脉宽控制可控硅的导通角，进而控制交流市电加载在PG电机上的交流电压值，实现PG电机的调速。由于可控硅在G极加载电压使可控硅导通时需要消耗一定的电流，同时给G极提供电压的12V端的限流电阻R6也存在发热损耗，因此给可控硅G极加载导通电压的时间不宜过长。由于电机内部的绕组线圈的电感特性，加载在电机上的交流电压和交流电流信号的相位不一致，如图2所示，当交流电压加载在电机上时，此时经过电机的电流的相位会滞后交流电压限位，如交流电压在一个工频周期的起始过零点0，对应交流电流信号在C1时刻才有过零，即这两个时刻不是同时的，当PG电机的转速比较高或者电机开始启动过程中，MCU输出的驱动脉冲的脉宽的起始点离电压过零信号比较近时，此时会出现其脉冲的结束点位于对应的电流过零点之前，这样原来从驱动脉冲起始点开始后可控硅导通，但在电流过零点C1时刻会导致可控硅关闭，此后在整个交流电压过零周期期间可控硅都处于关闭状态，而正常状态这期间可控硅是导通的，直到下个交流电压过零周期，有驱动脉冲时才可控硅才开始导通，如图2中所示，电机驱动信号的第一个脉冲位于交流输入电压的过零点和电机电流的过零点之间时，驱动信号脉冲的触发起始点时刻可控硅导通，对应电机输入端的有效电压C2点开始有电压加载在PG电机上，PG电机中有电流通过，电机开始运转，当到达电流过零信号的C1点时刻，由于此时电流过零，可控硅会关闭，由于驱动脉冲在C1点时刻以前已经关闭，这样从电流过零信号开始的整个交流电压过零周期期间可控硅都处于关闭状态，如图中电机输入端有效电压从C2到C3时刻的虚线部的有效电压为零，正常情况应该有效电压值一直存在，这样会导致可控硅出现意外的关闭，引起电机在启动或者高速运转时出现频繁的抖动，不能达到正常的转速。
上述内容仅用于辅助理解本发明的技术方案，并不代表承认上述内容是现有技术。
发明内容
本发明的主要目的在于提供一种基于交流电机控制电路的控制方法、装置及空调器，目的在于解决由于现有技术中驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，由于交流电流信号导致电机驱动功率器件关闭，从而引起交流电机在启动或者高速运行过程中出现频繁抖动而运行不稳定问题。
为实现上述目的，本发明提供的一种基于交流电机控制电路的控制方法，所述基于交流电机控制电路的控制方法包括以下步骤：
获取所述交流电机的目标转速；
检测所述交流电机控制电路输入电压的过零信号以及交流电机的实时转速反馈信号；
根据所述目标转速和实时转速反馈信号调整当前驱动脉冲信号的触发起始点，并控制当前驱动脉冲信号的结束点在所述的交流电流过零点时刻之后；其中，所述驱动脉冲信号以驱动所述交流电机运行达到目标转速。
优选的，所述根据所述目标转速和实时转速反馈信号调整当前驱动脉冲信号的触发起始点，并控制当前驱动脉冲信号的结束点在所述的交流电流过零点时刻之后的步骤包括：
根据所述目标转速和实时转速反馈信号调整当前驱动脉冲信号的触发起始点，且所述当前驱动脉冲信号的脉宽为预设的第一脉宽值，以使当前驱动脉冲信号的结束点在所述的交流电流过零点时刻之后。
优选的，所述根据所述目标转速和实时转速反馈信号调整当前驱动脉冲信号的触发起始点，并控制当前驱动脉冲信号的结束点在所述的交流电流过零点时刻之后的步骤包括：
获取下一个电压过零点时刻；
控制当前驱动脉冲信号的脉冲宽度为触发起始点至下一个电压过零点时刻之间的时间差。
优选的，所述根据所述目标转速和实时转速反馈信号调整当前驱动脉冲信号的触发起始点，并控制当前驱动脉冲信号的结束点在所述的交流电流过零点时刻之后的步骤包括：
判断所述的驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，控制所述驱动脉冲信号的结束点在交流电流过零点时刻之后。
优选的，所述判断所述的驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，控制所述驱动脉冲信号的结束点在所述交流电流过零点时刻之后的步骤包括：
判断所述的驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，获取本次交流输入电压周期对应的交流电流过零点时刻；
调整当前驱动脉冲信号的脉冲宽度，以使所述驱动脉冲信号的结束点在所述的交流电流过零点时刻之后。
优选的，所述根据所述目标转速和实时转速反馈信号调整当前驱动脉冲信号的触发起始点，并控制当前驱动脉冲信号的结束点在所述的交流电流过零点时刻之后的步骤还包括：
判断所述的驱动脉冲信号的触发起始点晚于本次交流输入电压周期对应的交流电流过零点时刻时，控制当前驱动脉冲信号的脉冲宽度为预设的第二脉冲宽度。
优选的，所述判断所述的驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，控制所述驱动脉冲信号的结束点在所述交流电流过零点时刻之后的步骤包括：
判断所述的驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，控制当前驱动脉冲信号的脉冲宽度为预设的第三脉冲宽度，以使所述驱动脉冲信号的结束点在所述的交流电流过零点时刻之后。
优选的，所述判断所述的驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，控制所述驱动脉冲信号的结束点在所述的交流电流过零点时刻之后的步骤包括：
判断所述的驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，获取下一个电压过零点时刻；
控制当前驱动脉冲信号的脉冲宽度为触发起始点至下一个电压过零点时刻之间的时间差。
优选的，所述根据所述目标转速和实时转速反馈信号调整当前驱动脉冲信号的触发起始点，并控制当前驱动脉冲信号的结束点在所述的交流电流过零点时刻之后的步骤还包括：
判断所述的驱动脉冲信号的触发起始点晚于本次交流输入电压周期对应的交流电流过零点时刻时，控制当前驱动脉冲信号的脉冲宽度为预设的第四脉冲宽度，且所述第四脉冲宽度大于当前的脉冲信号的脉冲宽度。
实现上述目的，本发明还提供的一种基于交流电机控制电路的控制装置，所述基于交流电机控制电路的控制装置包括：
获取模块，用于获取所述交流电机的目标转速；
检测模块，用于检测所述交流电机控制电路输入电压的过零信号以及交流电机的实时转速反馈信号；
控制模块，用于根据所述目标转速和实时转速反馈信号调整当前驱动脉冲信号的触发起始点，并控制当前驱动脉冲信号的结束点在所述的交流电流过零点时刻之后；其中，所述驱动脉冲信号以驱动所述交流电机运行达到目标转速。
优选的，所述控制模块还用于，
根据所述目标转速和实时转速反馈信号调整当前驱动脉冲信号的触发起始点，且所述当前驱动脉冲信号的脉宽为预设的第一脉宽值，以使当前驱动脉冲信号的结束点在所述的交流电流过零点时刻之后。
优选的，所述控制模块还用于，
获取下一个电压过零点时刻；
控制当前驱动脉冲信号的脉冲宽度为触发起始点至下一个电压过零点时刻之间的时间差。
优选的，所述控制模块还用于，
判断所述的驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，控制所述驱动脉冲信号的结束点在交流电流过零点时刻之后。
优选的，所述控制模块还用于，
判断所述的驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，获取本次交流输入电压周期对应的交流电流过零点时刻；
调整当前驱动脉冲信号的脉冲宽度，以使所述驱动脉冲信号的结束点在所述的交流电流过零点时刻之后。
优选的，所述控制模块还用于，
判断所述的驱动脉冲信号的触发起始点晚于本次交流输入电压周期对应的交流电流过零点时刻时，控制当前驱动脉冲信号的脉冲宽度为预设的第二脉冲宽度。
优选的，所述控制模块还用于，
判断所述的驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，控制当前驱动脉冲信号的脉冲宽度为预设的第三脉冲宽度，以使所述驱动脉冲信号的结束点在所述的交流电流过零点时刻之后。
优选的，所述控制模块还用于，
判断所述的驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，获取下一个电压过零点时刻；
控制当前驱动脉冲信号的脉冲宽度为触发起始点至下一个电压过零点时刻之间的时间差。
优选的，所述控制模块还用于，
判断所述的驱动脉冲信号的触发起始点晚于本次交流输入电压周期对应的交流电流过零点时刻时，控制当前驱动脉冲信号的脉冲宽度为预设的第四脉冲宽度，且所述第四脉冲宽度大于当前的脉冲信号的脉冲宽度。
实现上述目的，本发明还提供的一种空调器，所述空调器包括上述基于交流电机控制电路的控制装置。
本发明的交流电机控制电路通过获取所在设备的目标转速，通过其相关电路检测交流电机控制电路输入电压的过零信号以及交流电机的转速反馈信号，交流驱动电路中的MCU根据过零信号和转速反馈信号输出驱动脉冲信号，并根据所述目标转速和实时转速反馈信号输出调整当前驱动脉冲信号的触发起始点，控制所述驱动脉冲信号的结束点在所述的交流电流过零点时刻之后，解决了现有技术中交流电机在启动或者高速运转过程中，当交流电机控制电路的驱动脉冲信号处在上述情况中时，出现在其电流过零点时刻导致驱动电路中的可控硅等电机驱动的功率器件关闭引起交流电机运行时转速不稳和抖动的异常问题，保证了交流电机的平稳可靠的正常运行。
附图说明
图1为本发明针对现有技术的交流电机控制电路结构图；
图2为本发明针对现有技术的交流电机控制电路的波形图；
图3为本发明基于交流电机控制电路的控制方法的第一实施例的流程示意图；
图4为本发明基于交流电机控制电路的控制方法的第一、第三实施例的交流电机控制电路的波形图；
图5为本发明基于交流电机控制电路的控制方法的第二、第七实施例的交流电机控制电路的波形图；
图6为本发明基于交流电机控制电路的控制方法的第四实施例的另一交流电机控制电路的波形图；
图7为本发明基于交流电机控制电路的控制方法的第五、第六实施例的交流电机控制电路的波形图；
图8为本发明基于交流电机控制电路的控制方法的第八实施例的交流电机控制电路的波形图；
图9为本发明基于交流电机控制电路的控制装置的功能模块示意图。
本发明目的的实现、功能特点及优点将结合实施例，参照附图做进一步说明。
具体实施方式
应当理解，此处所描述的具体实施例仅仅用以解释本发明，并不用于限定本发明。
下面参照附图描述根据本发明实施例提出的基于交流电机控制电路的控制方法和控制装置。
首先对本发明基于交流电机控制电路的控制方法进行说明。图3为根据本发明的第一实施例的基于交流电机控制电路的控制方法流程图。如图3所示，本发明实施例的基于交流电机控制电路的控制方法包括以下步骤：
步骤S10，获取交流电机的目标转速。
目标转速一般由交流电机控制电路从其所在的设备获取，例如所述的交流电机控制电路用于空调器室内电机的驱动，空调器通过获取用户设置的当前风速档位或者风速等级，MCU再通过存储器调取其风速档位或者风速等级对应的目标转速值，这样就获取了当前的目标转速。
步骤S20，检测交流电机控制电路输入电压的过零信号以及交流电机的实时转速反馈信号；
如图1所述的交流电机控制电路，通过图中A部分电路实现交流输入电压的过零信号检测，主要基于光耦IC1实现过零检测，并通过三极管Q1整形后输入到MCU的P1端口实现检测，在P1端口得到如图2中所示的交流电压过零信号波形，图1中的B部分检测交流电机转速反馈信号，并输入到MCU的P3端口实现检测。
步骤S30，根据所述目标转速和实时转速反馈信号输出调整当前驱动脉冲信号的触发起始点，并控制当前驱动脉冲信号的结束点在所述的交流电流过零点时刻之后；其中，所述驱动脉冲信号以驱动所述交流电机运行达到目标转速。
MCU通过获取目标转速值，如用户设置空调器为低风档位，MCU通过调取存储器数据表格得到低风档位800转/分，并进一步根据过零信号的时刻，在本次过零信号后面的相对时间点给出初始的电机驱动脉冲信号，如图4中在C3时刻给出电机驱动脉冲信号，并结合当前电机的转速反馈信号，调整驱动脉冲信号在过零信号后的触发时刻位置，以调节电机的转速，达到目标转速值。
具体参照图4，电机驱动电路实时转速反馈信号获得当前的实时转速，并根据目标转速值调整当前驱动脉冲信号的触发起始点，如图中所示调整当前的驱动脉冲信号的触发起始点为C3时刻，图中电机在全电压时电流的第一个过零信号为C1时刻，晚于交流输入电压的第一个过零信号0时刻，当MCU输出脉冲信号时，控制输出脉冲信号的结束点在C1时刻之后，即图中控制驱动脉冲信号的结束点为C4，位于C1之后。由于驱动脉冲信号的结束点C4位于电流过零点C1之后，保证了当交流电机的电流过零时刻C1时，仍然有驱动脉冲信号，保证了可控硅仍然能持续导通，不会关闭，这样交流电机上仍然加载有效电压，即图中的C1到C5时刻仍然加载有效电压，保证了交流电机从脉冲信号的触发起始点C3开始一直到本次交流电压过零周期结束C5能得到持续加载有效电压，避免了现有技术中在这种情况下交流电机由于电流过零点时刻导致电机驱动功率器件如可控硅关闭，导致后续的交流电压过零周期内不能加载有效电压，引起电机转速不稳发生抖动的异常现象。
需要说明的是，为了信号展示的完整性，图中交流电机的电流信号为全电压加载在其上时的电流信号，即此时交流电机是在交流电压的全部周期内一直有效加载，通常为电机转速最大时的情况，此时电机的电流信号也在全部周期内都存在，二者的相位差别通过多个过零点能清楚的展示出来，当然也可以去电机当前转速的电流信号来展示，如果电机不是全电压加载，则电流信号必然存在不连续情况，如果要展示其过零点与交流输入电压过零点的对比就不太方便的形成对比。对不同型号的交流电机而言，由于存在电机线圈绕组及电机内部结构的差异，其电压和电流的相位差即过零点的时间差通常不同，对采用的具体一个型号的电机的其电压与电流过零点的时间差参数可以在试验中很容易获取，一般为一个范围值，可以取其范围值的最大值做为时间差参数，在控制时当MCU判断电机驱动脉冲信号的起始点时刻位于电压过零点时刻起到上述时间差之前时，就控制器脉冲信号的结束时刻在上述时间差之后。
MCU通过上述控制电机驱动脉冲信号以驱动所述交流电机运行达到目标转速，具体为：MCU输出驱动脉冲信号到交流电机驱动电路，其驱动电路根据驱动脉冲根据交流输入电压进行转换，加载在交流电机电源输入端，实现电机的正常运转。具体的可以参见图1中的C部分电路，MCU通过P2口输出驱动脉冲信号，其电机驱动电路主要以电机驱动功率器件组成，如图中的可控硅TR1，MCU输出的驱动脉冲信号通过三极管Q2对光耦IC3进行控制，光耦IC3对可控硅的G级根据脉冲信号进行触发，使得可控硅导通，当控制驱动脉冲信号的起始点位于交流电压过零周期内的不同时刻时，其可控硅的导通角不同，从而导致本周起内通过可控硅的交流电流不同，因此加载在交流电机上的交流电压有效值不同，从而改变电机的转速，并进一步结合交流电机的实时转速反馈信号，判断当前的转速是否与目标转速相同，当转速不同时，通过改变可控硅的导通角最终达到目标转速。
本实施例中，交流电机控制电路通过获取所在设备的目标转速，通过其相关电路检测交流电机控制电路输入电压的过零信号以及交流电机的转速反馈信号，交流驱动电路中的MCU根据过零信号和转速反馈信号输出驱动脉冲信号，并根据所述目标转速和实时转速反馈信号输出调整当前驱动脉冲信号的触发起始点，控制所述驱动脉冲信号的结束点在所述的交流电流过零点时刻之后，避免了交流电机在启动或者高速运转过程中，当交流电机控制电路的驱动脉冲信号处在上述情况中时，出现在其电流过零点时刻导致驱动电路中的可控硅等电机驱动的功率器件关闭引起交流电机运行时转速不稳和抖动的异常问题，保证了交流电机的平稳可靠的正常运行。
进一步的，基于交流电机控制电路的控制方法的第二实施例，基于上述本发明基于交流电机控制电路的控制方法第一实施例，在本实施例中，根据目标转速和实时转速反馈信号调整当前驱动脉冲信号的触发起始点，且所述当前驱动脉冲信号的脉宽为预设的第一脉宽值，以使得驱动脉冲信号的结束点在所述的交流电流过零点时刻之后，即控制当前驱动脉冲信号的脉宽为预设的固定脉宽值。
具体参见图4，图中电机驱动脉冲信号的脉宽为固定值，如图中第一个电机驱动脉冲信号的触发起始点C3，结束点是C4，位于交流电机过零点C1之后，其脉宽为C3到C4之间第一脉宽值T1，其他驱动脉冲信号的脉宽都为此第一脉宽值，由于驱动脉冲信号的脉宽为固定的第一脉宽值，MCU控制输出脉宽时会相对简单，且能进一步可靠保证在交流电流过零点之后交流电机控制电路的电机驱动功率器件如可控硅还能持续开通，保证了电机的正常运转，实际应用中，此第一脉宽值取值范围是1<T1<8ms。
进一步的，本实施例中控制所述驱动脉冲信号的结束点还可以进一步细分控制，本实施例中，进一步获取下一个电压过零点时刻，控制当前驱动脉冲信号的脉冲宽度为触发起始点至下一个电压过零点时刻之间的时间差。
具体参见图5，当驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，具体图纸第一个电机驱动脉冲信号的触发起始点C3位于本次交流电压周期对应的交流电流过零点C1之前，此时MCU控制电机驱动脉冲信号的结束点是下一个电压过零点即C5时刻，也就是电机驱动脉冲信号从触发起始点开始一直到本次交流电压过零周期才结束，由于本次交流电压周期对应的交流电流过零点是在其电压过零周期内的，这样能可靠的保证在交流电流过零点之后交流电机控制电路的电机驱动功率器件如可控硅还能持续开通，即从驱动脉冲的触发起始点开始一直到本次过零电压周期结束都能持续开通，此时间内电机输入端的有效电压一直加载，如图中C3到C5时刻之间电机输入端有效电压一直有波形存在，保证了电机的正常运转。
进一步的，基于交流电机控制电路的控制方法的第三实施例，基于上述本发明基于交流电机控制电路的控制方法第一实施例，在本实施例中，判断所述的驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，控制所述驱动脉冲信号的结束点在所述的交流电流过零点时刻之后；根据所述驱动脉冲信号驱动交流电机运行达到目标转速。
具体参照图4，图中电机在全电压时电流的第一个过零信号为C1时刻，晚于交流输入电压的第一个过零信号0时刻，当MCU根据上述S30步骤输出脉冲信号时，判断其脉冲信号的触发起始点是否在C1时刻之前，如果在之前，则控制输出脉冲信号的结束点在C1时刻之后，即图中电机驱动脉冲信号的触发起始点为C3，位于C1时刻之前，则控制驱动脉冲信号的结束点为C4，位于C1之后。由于驱动脉冲信号的结束点C4位于电流过零点C1之后，保证了当交流电机的电流过零时刻C1时，仍然有驱动脉冲信号，保证了可控硅仍然能持续导通，不会关闭，这样交流电机上仍然加载有效电压，即图中的C1到C5时刻仍然加载有效电压，保证了交流电机从脉冲信号的触发起始点C3开始一直到本次交流电压过零周期结束C5能得到持续加载有效电压，避免了现有技术中在这种情况下交流电机由于电流过零点时刻导致电机驱动功率器件如可控硅关闭，导致后续的交流电压过零周期内不能加载有效电压，引起电机转速不稳发生抖动的异常现象。
进一步的，基于交流电机控制电路的控制方法的第四实施例，基于上述本发明基于交流电机控制电路的控制方法第三实施例，在本实施例中，判断所述的驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，获取本次交流输入电压周期对应的交流电流过零点时刻；
调整当前驱动脉冲信号的脉冲宽度，以使所述驱动脉冲信号的结束点在所述的交流电流过零点时刻之后。
在本实施例中，当MCU判断驱动脉冲信号的触发起始点时间早于本次交流电机的电流过零点时刻时，通过获取本次交流输入电压周期对应的交流电流过零点时刻，并调整调整当前驱动脉冲信号的脉冲宽度，即其驱动脉冲信号的脉宽可变化。由于交流电机的目标转速不同，MCU根据目标转速和实时转速反馈信号输出驱动脉冲信号时，其脉冲信号的触发起始点会有不同，而当驱动脉冲信号的触发起始点时间早于本次交流电机的电流过零点时刻时，为了保证在交流电机的电流过零时刻，电机驱动功率器件能持续导通不被关断，因此需要控制驱动脉冲信号结束点在所述的交流电流过零点时刻之后，具体的只要结束点在交流电流的过零点之后的一个很小的预设时间差的固定时刻即可，即只要能保证电机驱动功率器件在交流电流的过零点时刻能持续导通即可，这样由于驱动脉冲信号的触发起始点是可变的，而结束时刻是固定的，因此驱动脉冲的脉宽是可变化的。具体如图6所示，电机驱动信号的第1个脉冲到第3个驱动脉冲的触发起始点都不同，而其脉冲的结束点都是一个固定时刻，在每个电流过零点时刻之后，因此其脉宽都不同，如当交流电机的转速升高，即加载在电机上的交流电压有效值需要逐渐升高时，其驱动脉冲的触发起始点逐渐接近本本周内的电压过零点，如图中第1个到第3个脉冲的触发起始点距离交流输入电压的第一个过零点逐渐接近，这样驱动脉冲的脉宽逐渐变长，每个脉宽都是不同的，即图中脉宽T2<T3<T4。此处理方案能保证在交流电机的电流过零时刻时，电机驱动功率器件仍然持续导通情况下，做得其驱动脉冲的脉宽尽量的窄，进一步减小功率器件的损耗电流。
进一步的，基于交流电机控制电路的控制方法的第五实施例，基于上述本发明基于交流电机控制电路的控制方法第三或第四实施例，在本实施例中，判断所述的驱动脉冲信号的触发起始点晚于本次交流输入电压周期对应的交流电流过零点时刻时，控制当前驱动脉冲信号的脉冲宽度为预设的第二脉冲宽度。
本实施例中，MCU判断驱动脉冲信号的触发起始点晚于本次交流输入电压周期对应的交流电流过零点时刻时，MCU控制所述驱动脉冲信号的脉宽改变为第二脉冲宽度，即为固定时间值，如图7中基于第三实施例，第4个脉冲信号的结束点位于本次交流输入电压周期对应的交流电流过零点之后时，其脉冲脉宽调整为固定时间值，其脉宽为固定时间值T5，或者如图6中基于第四实施例，第4个脉冲脉宽也为固定时间值T5，由于脉冲信号的触发起始点是晚于本次交流输入电压周期对应的交流电流过零点时刻时，本次过零交流电压的过零信号周期内，即前一个过零电压信号到下一个电压过零信号的时间内，不存在电流过零引起电机驱动功率器件关闭的情况，因此其驱动脉冲信号的脉宽可以减小，只要能保证驱动脉冲信号能正常触发电机驱动功率器件如可控硅导通即可，脉冲信号的脉宽减小，能进一步减小功率器件的损耗电流。实际应用中，此第一脉宽值取值范围是100<T5<800us。
进一步的，基于交流电机控制电路的控制方法的第六实施例，基于上述本发明基于交流电机控制电路的控制方法第三实施例，在本实施例中，判断所述的驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，控制当前驱动脉冲信号的脉冲宽度为预设的第三脉冲宽度，以使所述驱动脉冲信号的结束点在所述的交流电流过零点时刻之后。
具体参见图4，图中电机驱动脉冲信号的脉宽为预设的第三脉冲宽度，即为预设的固定值，如图中第一个电机驱动脉冲信号的触发起始点C3，结束点是C4，位于交流电机过零点C1之后，其脉宽为C3到C4之间第一脉宽值，其他驱动脉冲信号的脉宽都为此第三脉宽值T1，由于驱动脉冲信号的脉宽为固定的第三脉宽值，MCU控制输出脉宽时会相对简单，且能进一步可靠保证在交流电流过零点之后交流电机控制电路的电机驱动功率器件如可控硅还能持续开通，保证了电机的正常运转。实际应用中，此第一脉宽值取值范围是1<T1<8ms。
进一步的，基于交流电机控制电路的控制方法的第七实施例，基于上述本发明基于交流电机控制电路的控制方法第三实施例，判断所述的驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，获取下一个电压过零点时刻；控制当前驱动脉冲信号的脉冲宽度为触发起始点至下一个电压过零点时刻之间的时间差。
具体参见图5，当MCU判断当前驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，通过检测下一个电压过零点时刻，MCU控制当前的驱动脉冲信号的结束点为电压过零点时刻，具体图纸第一个电机驱动脉冲信号的触发起始点C3位于本次交流电压周期对应的交流电流过零点C1之前，此时MCU控制电机驱动脉冲信号的结束点是下一个电压过零点即C5时刻，也就是电机驱动脉冲信号从触发起始点开始一直到本次交流电压过零周期才结束，由于本次交流电压周期对应的交流电流过零点是在其电压过零周期内的，这样能可靠的保证在交流电流过零点之后交流电机控制电路的电机驱动功率器件如可控硅还能持续开通，即从驱动脉冲的触发起始点开始一直到本次过零电压周期结束都能持续开通，此时间内电机输入端的有效电压一直加载，如图中C3到C5时刻之间电机输入端有效电压一直有波形存在，保证了电机的正常运转。
进一步的，基于交流电机控制电路的控制方法的第八实施例，基于上述本发明基于交流电机控制电路的控制方法第六或第七实施例，判断所述的驱动脉冲信号的触发起始点晚于本次交流输入电压周期对应的交流电流过零点时刻时，控制当前驱动脉冲信号的脉冲宽度为预设的第四脉冲宽度，且所述第四脉冲宽度大于当前的脉冲信号的脉冲宽度。
实施例中，MCU判断驱动脉冲信号的触发起始点晚于本次交流输入电压周期对应的交流电流过零点时刻时，MCU控制所述驱动脉冲信号的脉宽改变为第二脉冲宽度，即为固定时间值，如图7中基于第六实施例，第4个脉冲信号的结束点位于本次交流输入电压周期对应的交流电流过零点之后时，其脉冲脉宽调整为固定时间值，其脉宽为固定时间值T5，或者如图8中基于第七实施例，第4个脉冲脉宽也为固定时间值T5，由于脉冲信号的触发起始点是晚于本次交流输入电压周期对应的交流电流过零点时刻时，本次过零交流电压的过零信号周期内，即前一个过零电压信号到下一个电压过零信号的时间内，不存在电流过零引起电机驱动功率器件关闭的情况，因此其驱动脉冲信号的脉宽可以减小，只要能保证驱动脉冲信号能正常触发电机驱动功率器件如可控硅导通即可，脉冲信号的脉宽减小，能进一步减小功率器件的损耗电流。实际应用中，此第一脉宽值取值范围是100<T5<800us。在图7中，MCU判断驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，对应其中的第一到第三个驱动脉冲，此脉冲信号为预设的第三脉宽值T3，当MCU判断驱动脉冲信号的触发起始点晚于本次交流输入电压周期对应的交流电流过零点时刻时，为了可靠保证在交流电流过零点之后交流电机控制电路的电机驱动功率器件如可控硅还能持续开通，则预设的第三脉宽值T3要大于T5，实际应用中，T3取值范围是1<T3<8ms，T5取值范围是100<T5<800us。在图8中，MCU判断驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，MCU当前驱动脉冲信号的脉冲宽度为触发起始点至下一个电压过零点时刻之间的时间差，则此当前的驱动脉冲的脉宽也要大于T5。
本发明还提供一种基于交流电机控制电路的控制装置。
参照图9，图9为本发明基于可穿戴设备的空调器控制装置第一实施例的功能模块示意图。
在本实施例中，所述基于可穿戴设备的空调器控制装置包括：
获取模块1，用于获取交流电机的目标转速；
检测模块2，用于检测交流电机控制电路输入电压的过零信号以及交流电机的实时转速反馈信号；
控制模块3，用于根据目标转速和实时转速反馈信号调整当前驱动脉冲信号的触发起始点，并控制当前驱动脉冲信号的结束点在交流电流过零点时刻之后；其中，所述驱动脉冲信号以驱动交流电机运行达到目标转速。
目标转速一般由交流电机控制电路从其所在的设备获取，例如所述的交流电机控制电路用于空调器室内电机的驱动，空调器通过获取用户设置的当前风速档位，MCU再通过调取存储的对应的目标转速值，这样获取模块1就获取了当前的目标转速。
如图1所述的交流电机控制电路，通过图中A部分电路实现交流输入电压的过零信号检测，主要基于光耦IC1实现过零检测，并通过三极管Q1整形后输入到MCU的P1端口实现检测，在P1端口得到如图2中所示的交流电压过零信号波形，图1中的B部分检测交流电机转速反馈信号，并输入到MCU的P3端口实现检测。
MCU通过获取目标转速值，如用户设置空调器为低风档位，MCU通过调取存储器数据表格得到低风档位800转/分，并进一步根据过零信号的时刻，再本次过零信号后面的相对时间点给出初始的电机驱动脉冲信号，如图4中在C3时刻给出电机驱动脉冲信号，并结合当前电机的转速反馈信号，调整驱动脉冲信号在过零信号后的触发时刻位置，以调节电机的转速，达到目标转速值。
具体参照图4，电机驱动电路实时转速反馈信号获得当前的实时转速，并根据目标转速值调整当前驱动脉冲信号的触发起始点，如图中所示调整当前的驱动脉冲信号的触发起始点为C3时刻，图中电机在全电压时电流的第一个过零信号为C1时刻，晚于交流输入电压的第一个过零信号0时刻，当MCU输出脉冲信号时，控制输出脉冲信号的结束点在C1时刻之后，即图中控制驱动脉冲信号的结束点为C4，位于C1之后。由于驱动脉冲信号的结束点C4位于电流过零点C1之后，保证了当交流电机的电流过零时刻C1时，仍然有驱动脉冲信号，保证了可控硅仍然能持续导通，不会关闭，这样交流电机上仍然加载有效电压，即图中的C1到C5时刻仍然加载有效电压，保证了交流电机从脉冲信号的触发起始点C3开始一直到本次交流电压过零周期结束C5能得到持续加载有效电压，避免了现有技术中在这种情况下交流电机由于电流过零点时刻导致电机驱动功率器件如可控硅关闭，导致后续的交流电压过零周期内不能加载有效电压，引起电机转速不稳发生抖动的异常现象。
需要说明的是，为了信号展示的完整性，图中交流电机的电流信号为全电压加载在其上时的电流信号，即此时交流电机是在电压的全部周期内一直有效加载，通常为电机转速最大时的情况，此时电机的电流信号也在全部周期内都存在，二者的相位差别通过多个过零点能清楚的展示出来，当然也可以去电机当前转速的电流信号来展示，如果电机不是全电压加载，则电流信号必然存在不连续情况，如果要展示其过零点与交流输入电压过零点的对比就不太方便的形成对比。对不同型号的交流电机而言，由于存在电机线圈绕组及电机内部结构的差异，其电压和电流的相位差即过零点的时间差通常不同，对采用的具体一个型号的电机的其电压与电流过零点的时间差参数可以在试验中很容易获取，一般为一个范围值，可以取其范围值的最大值做为时间差参数，在控制时当MCU判断电机驱动脉冲信号的起始点时刻位于电压过零点时刻起到上述时间差之前时，就控制器脉冲信号的结束时刻在上述时间差之后。
MCU通过上述控制电机驱动脉冲信号以驱动所述交流电机运行达到目标转速，具体为：MCU输出驱动脉冲信号到交流电机驱动电路，其驱动电路根据驱动脉冲根据交流输入电压进行转换，加载在交流电机电源输入端，实现电机的正常运转。具体的可以参见图1中的C部分电路，MCU通过P2口输出驱动脉冲信号，其电机驱动电路主要以电机驱动功率器件组成，如图中的可控硅TR1，MCU输出的驱动脉冲信号通过三极管Q2对光耦IC3进行控制，光耦IC3对可控硅的G级根据脉冲信号进行触发，使得可控硅导通，当控制驱动脉冲信号的起始点位于交流电压过零周期内的不同时刻时，其可控硅的导通角不同，从而导致本周起内通过可控硅的交流电流不同，因此加载在交流电机上的交流电压有效值不同，从而改变电机的转速，并进一步结合交流电机的实时转速反馈信号，判断当前的转速是否与目标转速相同，当转速不同时，通过改变可控硅的导通角最终达到目标转速。
本实施例中，交流电机控制电路通过获取所在设备的目标转速，通过其相关电路检测交流电机控制电路输入电压的过零信号以及交流电机的转速反馈信号，交流驱动电路中的MCU根据过零信号和转速反馈信号输出驱动脉冲信号，并根据所述目标转速和实时转速反馈信号输出调整当前驱动脉冲信号的触发起始点，控制所述驱动脉冲信号的结束点在所述的交流电流过零点时刻之后，避免了交流电机在启动或者高速运转过程中，当交流电机控制电路的驱动脉冲信号处在上述情况中时，出现在其电流过零点时刻导致驱动电路中的可控硅等电机驱动的功率器件关闭引起交流电机运行时转速不稳和抖动的异常问题，保证了交流电机的平稳可靠的正常运行。
进一步的，基于交流电机控制电路的控制装置的第二实施例，基于上述本发明基于交流电机控制电路的控制方法第一实施例，在本实施例中，根据目标转速和实时转速反馈信号调整当前驱动脉冲信号的触发起始点，且所述当前驱动脉冲信号的脉宽为预设的第一脉宽值，以使得驱动脉冲信号的结束点在所述的交流电流过零点时刻之后，即控制当前驱动脉冲信号的脉宽为预设的固定脉宽值。
具体参见图4，图中电机驱动脉冲信号的脉宽为固定值，如图中第一个电机驱动脉冲信号的触发起始点C3，结束点是C4，位于交流电机过零点C1之后，其脉宽为C3到C4之间第一脉宽值T1，其他驱动脉冲信号的脉宽都为此第一脉宽值，由于驱动脉冲信号的脉宽为固定的第一脉宽值，MCU控制输出脉宽时会相对简单，且能进一步可靠保证在交流电流过零点之后交流电机控制电路的电机驱动功率器件如可控硅还能持续开通，保证了电机的正常运转，实际应用中，此第一脉宽值取值范围是1<T1<8ms。
进一步的，本实施例中控制所述驱动脉冲信号的结束点还可以进一步细分控制，本实施例中，进一步获取下一个电压过零点时刻，控制当前驱动脉冲信号的脉冲宽度为触发起始点至下一个电压过零点时刻之间的时间差。
具体参见图5，当驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，具体图纸第一个电机驱动脉冲信号的触发起始点C3位于本次交流电压周期对应的交流电流过零点C1之前，此时MCU控制电机驱动脉冲信号的结束点是下一个电压过零点即C5时刻，也就是电机驱动脉冲信号从触发起始点开始一直到本次交流电压过零周期才结束，由于本次交流电压周期对应的交流电流过零点是在其电压过零周期内的，这样能可靠的保证在交流电流过零点之后交流电机控制电路的电机驱动功率器件如可控硅还能持续开通，即从驱动脉冲的触发起始点开始一直到本次过零电压周期结束都能持续开通，此时间内电机输入端的有效电压一直加载，如图中C3到C5时刻之间电机输入端有效电压一直有波形存在，保证了电机的正常运转。
进一步的，基于交流电机控制电路的控制装置的第三实施例，基于上述本发明基于交流电机控制电路的控制装置第一实施例，在本实施例中，判断所述的驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，控制所述驱动脉冲信号的结束点在所述的交流电流过零点时刻之后；根据所述驱动脉冲信号驱动交流电机运行达到目标转速。
具体参照图4，图中电机在全电压时电流的第一个过零信号为C1时刻，晚于交流输入电压的第一个过零信号0时刻，当MCU根据上述S30步骤输出脉冲信号时，判断其脉冲信号的触发起始点是否在C1时刻之前，如果在之前，则控制输出脉冲信号的结束点在C1时刻之后，即图中电机驱动脉冲信号的触发起始点为C3，位于C1时刻之前，则控制驱动脉冲信号的结束点为C4，位于C1之后。由于驱动脉冲信号的结束点C4位于电流过零点C1之后，保证了当交流电机的电流过零时刻C1时，仍然有驱动脉冲信号，保证了可控硅仍然能持续导通，不会关闭，这样交流电机上仍然加载有效电压，即图中的C1到C5时刻仍然加载有效电压，保证了交流电机从脉冲信号的触发起始点C3开始一直到本次交流电压过零周期结束C5能得到持续加载有效电压，避免了现有技术中在这种情况下交流电机由于电流过零点时刻导致电机驱动功率器件如可控硅关闭，导致后续的交流电压过零周期内不能加载有效电压，引起电机转速不稳发生抖动的异常现象。
进一步的，基于交流电机控制电路的控制装置的第四实施例，基于上述本发明基于交流电机控制电路的控制装置第三实施例，在本实施例中，判断所述的驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，获取本次交流输入电压周期对应的交流电流过零点时刻；
调整当前驱动脉冲信号的脉冲宽度，以使所述驱动脉冲信号的结束点在所述的交流电流过零点时刻之后。
在本实施例中，当MCU判断驱动脉冲信号的触发起始点时间早于本次交流电机的电流过零点时刻时，通过获取本次交流输入电压周期对应的交流电流过零点时刻，并调整调整当前驱动脉冲信号的脉冲宽度，即其驱动脉冲信号的脉宽可变化。由于交流电机的目标转速不同，MCU根据目标转速和实时转速反馈信号输出驱动脉冲信号时，其脉冲信号的触发起始点会有不同，而当驱动脉冲信号的触发起始点时间早于本次交流电机的电流过零点时刻时，为了保证在交流电机的电流过零时刻，电机驱动功率器件能持续导通不被关断，因此需要控制驱动脉冲信号结束点在所述的交流电流过零点时刻之后，具体的只要结束点在交流电流的过零点之后的一个很小的预设时间差的固定时刻即可，即只要能保证电机驱动功率器件在交流电流的过零点时刻能持续导通即可，这样由于驱动脉冲信号的触发起始点是可变的，而结束时刻是固定的，因此驱动脉冲的脉宽是可变化的。具体如图6所示，电机驱动信号的第1个脉冲到第3个驱动脉冲的触发起始点都不同，而其脉冲的结束点都是一个固定时刻，在每个电流过零点时刻之后，因此其脉宽都不同，如当交流电机的转速升高，即加载在电机上的交流电压有效值需要逐渐升高时，其驱动脉冲的触发起始点逐渐接近本本周内的电压过零点，如图中第1个到第3个脉冲的触发起始点距离交流输入电压的第一个过零点逐渐接近，这样驱动脉冲的脉宽逐渐变长，每个脉宽都是不同的，即图中脉宽T2<T3<T4。此处理方案能保证在交流电机的电流过零时刻时，电机驱动功率器件仍然持续导通情况下，做得其驱动脉冲的脉宽尽量的窄，进一步减小功率器件的损耗电流。
进一步的，基于交流电机控制电路的控制装置的第五实施例，基于上述本发明基于交流电机控制电路的控制装置第三或第四实施例，在本实施例中，判断所述的驱动脉冲信号的触发起始点晚于本次交流输入电压周期对应的交流电流过零点时刻时，控制当前驱动脉冲信号的脉冲宽度为预设的第二脉冲宽度。
本实施例中，MCU判断驱动脉冲信号的触发起始点晚于本次交流输入电压周期对应的交流电流过零点时刻时，MCU控制所述驱动脉冲信号的脉宽改变为第二脉冲宽度，即为固定时间值，如图7中基于第三实施例，第4个脉冲信号的结束点位于本次交流输入电压周期对应的交流电流过零点之后时，其脉冲脉宽调整为固定时间值，其脉宽为固定时间值T5，或者如图6中基于第四实施例，第4个脉冲脉宽也为固定时间值T5，由于脉冲信号的触发起始点是晚于本次交流输入电压周期对应的交流电流过零点时刻时，本次过零交流电压的过零信号周期内，即前一个过零电压信号到下一个电压过零信号的时间内，不存在电流过零引起电机驱动功率器件关闭的情况，因此其驱动脉冲信号的脉宽可以减小，只要能保证驱动脉冲信号能正常触发电机驱动功率器件如可控硅导通即可，脉冲信号的脉宽减小，能进一步减小功率器件的损耗电流。实际应用中，此第一脉宽值取值范围是100<T5<800us。
进一步的，基于交流电机控制电路的控制装置的第六实施例，基于上述本发明基于交流电机控制电路的控制装置第三实施例，在本实施例中，判断所述的驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，控制当前驱动脉冲信号的脉冲宽度为预设的第三脉冲宽度，以使所述驱动脉冲信号的结束点在所述的交流电流过零点时刻之后。
具体参见图4，图中电机驱动脉冲信号的脉宽为预设的第三脉冲宽度，即为预设的固定值，如图中第一个电机驱动脉冲信号的触发起始点C3，结束点是C4，位于交流电机过零点C1之后，其脉宽为C3到C4之间第一脉宽值，其他驱动脉冲信号的脉宽都为此第三脉宽值T1，由于驱动脉冲信号的脉宽为固定的第三脉宽值，MCU控制输出脉宽时会相对简单，且能进一步可靠保证在交流电流过零点之后交流电机控制电路的电机驱动功率器件如可控硅还能持续开通，保证了电机的正常运转。实际应用中，此第一脉宽值取值范围是1<T1<8ms。
进一步的，基于交流电机控制电路的控制装置的第七实施例，基于上述本发明基于交流电机控制电路的控制装置第三实施例，判断所述的驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，获取下一个电压过零点时刻；控制当前驱动脉冲信号的脉冲宽度为触发起始点至下一个电压过零点时刻之间的时间差。
具体参见图5，当MCU判断当前驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，通过检测下一个电压过零点时刻，MCU控制当前的驱动脉冲信号的结束点为电压过零点时刻，具体图纸第一个电机驱动脉冲信号的触发起始点C3位于本次交流电压周期对应的交流电流过零点C1之前，此时MCU控制电机驱动脉冲信号的结束点是下一个电压过零点即C5时刻，也就是电机驱动脉冲信号从触发起始点开始一直到本次交流电压过零周期才结束，由于本次交流电压周期对应的交流电流过零点是在其电压过零周期内的，这样能可靠的保证在交流电流过零点之后交流电机控制电路的电机驱动功率器件如可控硅还能持续开通，即从驱动脉冲的触发起始点开始一直到本次过零电压周期结束都能持续开通，此时间内电机输入端的有效电压一直加载，如图中C3到C5时刻之间电机输入端有效电压一直有波形存在，保证了电机的正常运转。
进一步的，基于交流电机控制电路的控制装置的第八实施例，基于上述本发明基于交流电机控制电路的控制装置第六或第七实施例，判断所述的驱动脉冲信号的触发起始点晚于本次交流输入电压周期对应的交流电流过零点时刻时，控制当前驱动脉冲信号的脉冲宽度为预设的第四脉冲宽度，且所述第四脉冲宽度大于当前的脉冲信号的脉冲宽度。
实施例中，MCU判断驱动脉冲信号的触发起始点晚于本次交流输入电压周期对应的交流电流过零点时刻时，MCU控制所述驱动脉冲信号的脉宽改变为第二脉冲宽度，即为固定时间值，如图7中基于第六实施例，第4个脉冲信号的结束点位于本次交流输入电压周期对应的交流电流过零点之后时，其脉冲脉宽调整为固定时间值，其脉宽为固定时间值T5，或者如图8中基于第七实施例，第4个脉冲脉宽也为固定时间值T5，由于脉冲信号的触发起始点是晚于本次交流输入电压周期对应的交流电流过零点时刻时，本次过零交流电压的过零信号周期内，即前一个过零电压信号到下一个电压过零信号的时间内，不存在电流过零引起电机驱动功率器件关闭的情况，因此其驱动脉冲信号的脉宽可以减小，只要能保证驱动脉冲信号能正常触发电机驱动功率器件如可控硅导通即可，脉冲信号的脉宽减小，能进一步减小功率器件的损耗电流。实际应用中，此第一脉宽值取值范围是100<T5<800us。在图7中，MCU判断驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，对应其中的第一到第三个驱动脉冲，此脉冲信号为预设的第三脉宽值T3，当MCU判断驱动脉冲信号的触发起始点晚于本次交流输入电压周期对应的交流电流过零点时刻时，为了可靠保证在交流电流过零点之后交流电机控制电路的电机驱动功率器件如可控硅还能持续开通，则预设的第三脉宽值T3要大于T5，实际应用中，T3取值范围是1<T3<8ms，T5取值范围是100<T5<800us。在图8中，MCU判断驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，MCU当前驱动脉冲信号的脉冲宽度为触发起始点至下一个电压过零点时刻之间的时间差，则此当前的驱动脉冲的脉宽也要大于T5。
本发明还提供一种空调器。
在本实施例中，所述的空调器除了包含现有技术中提到的各个部件及控制电路外，还包括上述基于交流电机控制电路的控制装置，用于控制空调器的室内或者室外风机的运行。
本实施例中，所述空调器的交流电机控制电路通过获取所在设备的目标转速，通过其相关电路检测交流电机控制电路输入电压的过零信号以及交流电机的转速反馈信号，交流驱动电路中的MCU根据过零信号和转速反馈信号输出驱动脉冲信号，并根据所述目标转速和实时转速反馈信号输出调整当前驱动脉冲信号的触发起始点，并根据所述目标转速和实时转速反馈信号输出调整当前驱动脉冲信号的触发起始点，避免了交流电机在启动或者高速运转过程中，当交流电机控制电路的驱动脉冲信号处在上述情况中时，出现在其电流过零点时刻导致驱动电路中的可控硅等电机驱动的功率器件关闭引起交流电机运行时转速不稳和抖动的异常问题，保证了交流电机的平稳可靠的正常运行。
以上仅为本发明的优选实施例，并非因此限制本发明的专利范围，凡是利用本发明说明书及附图内容所作的等效结构或等效流程变换，或直接或间接运用在其他相关的技术领域，均同理包括在本发明的专利保护范围内。

Claims (19)

  1. 一种基于交流电机控制电路的控制方法，其特征在，所述用于交流电机控制电路的控制方法包括以下步骤：
    获取所述交流电机的目标转速；
    检测所述交流电机控制电路输入电压的过零信号以及交流电机的实时转速反馈信号；
    根据所述目标转速和实时转速反馈信号调整当前驱动脉冲信号的触发起始点，并控制当前驱动脉冲信号的结束点在所述的交流电流过零点时刻之后；其中，所述驱动脉冲信号以驱动所述交流电机运行达到目标转速。
  2. 如权利要求1所述的基于交流电机控制电路的控制方法，其特征在于，所述根据所述目标转速和实时转速反馈信号调整当前驱动脉冲信号的触发起始点，并控制当前驱动脉冲信号的结束点在所述的交流电流过零点时刻之后的步骤包括：
    根据所述目标转速和实时转速反馈信号调整当前驱动脉冲信号的触发起始点，且所述当前驱动脉冲信号的脉宽为预设的第一脉宽值，以使当前驱动脉冲信号的结束点在所述的交流电流过零点时刻之后。
  3. 如权利要求1所述的基于交流电机控制电路的控制方法，其特征在于，所述根据所述目标转速和实时转速反馈信号调整当前驱动脉冲信号的触发起始点，并控制当前驱动脉冲信号的结束点在所述的交流电流过零点时刻之后的步骤包括：
    获取下一个电压过零点时刻；
    控制当前驱动脉冲信号的脉冲宽度为触发起始点至下一个电压过零点时刻之间的时间差。
  4. 如权利要求1所述的基于交流电机控制电路的控制方法，其特征在于，所述根据所述目标转速和实时转速反馈信号调整当前驱动脉冲信号的触发起始点，并控制当前驱动脉冲信号的结束点在所述的交流电流过零点时刻之后的步骤包括：
    判断所述的驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，控制所述驱动脉冲信号的结束点在交流电流过零点时刻之后。
  5. 如权利要求4所述的用于交流电机控制电路的控制方法，其特征在于，所述判断所述的驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，控制所述驱动脉冲信号的结束点在所述交流电流过零点时刻之后的步骤包括：
    判断所述的驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，获取本次交流输入电压周期对应的交流电流过零点时刻；
    调整当前驱动脉冲信号的脉冲宽度，以使所述驱动脉冲信号的结束点在所述的交流电流过零点时刻之后。
  6. 如权利要求4所述的用于交流电机控制电路的控制方法，其特征在于，所述根据所述目标转速和实时转速反馈信号调整当前驱动脉冲信号的触发起始点，并控制当前驱动脉冲信号的结束点在所述的交流电流过零点时刻之后的步骤还包括：
    判断所述的驱动脉冲信号的触发起始点晚于本次交流输入电压周期对应的交流电流过零点时刻时，控制当前驱动脉冲信号的脉冲宽度为预设的第二脉冲宽度。
  7. 如权利要求5所述的用于交流电机控制电路的控制方法，其特征在于，所述根据所述目标转速和实时转速反馈信号调整当前驱动脉冲信号的触发起始点，并控制当前驱动脉冲信号的结束点在所述的交流电流过零点时刻之后的步骤还包括：
    判断所述的驱动脉冲信号的触发起始点晚于本次交流输入电压周期对应的交流电流过零点时刻时，控制当前驱动脉冲信号的脉冲宽度为预设的第二脉冲宽度。
  8. 如权利要求4所述的用于交流电机控制电路的控制方法，其特征在于，所述判断所述的驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，控制所述驱动脉冲信号的结束点在所述交流电流过零点时刻之后的步骤包括：
    判断所述的驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，控制当前驱动脉冲信号的脉冲宽度为预设的第三脉冲宽度，以使所述驱动脉冲信号的结束点在所述的交流电流过零点时刻之后。
  9. 如权利要求4所述的用于交流电机控制电路的控制方法，其特征在于，所述判断所述的驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，控制所述驱动脉冲信号的结束点在所述的交流电流过零点时刻之后的步骤包括：
    判断所述的驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，获取下一个电压过零点时刻；
    控制当前驱动脉冲信号的脉冲宽度为触发起始点至下一个电压过零点时刻之间的时间差。
  10. 如权利要求8所述的用于交流电机控制电路的控制方法，其特征在于，所述根据所述目标转速和实时转速反馈信号调整当前驱动脉冲信号的触发起始点，并控制当前驱动脉冲信号的结束点在所述的交流电流过零点时刻之后的步骤还包括：
    判断所述的驱动脉冲信号的触发起始点晚于本次交流输入电压周期对应的交流电流过零点时刻时，控制当前驱动脉冲信号的脉冲宽度为预设的第四脉冲宽度，且所述第四脉冲宽度大于当前的脉冲信号的脉冲宽度。
  11. 如权利要求9所述的用于交流电机控制电路的控制方法，其特征在于，所述根据所述目标转速和实时转速反馈信号调整当前驱动脉冲信号的触发起始点，并控制当前驱动脉冲信号的结束点在所述的交流电流过零点时刻之后的步骤还包括：
    判断所述的驱动脉冲信号的触发起始点晚于本次交流输入电压周期对应的交流电流过零点时刻时，控制当前驱动脉冲信号的脉冲宽度为预设的第四脉冲宽度，且所述第四脉冲宽度大于当前的脉冲信号的脉冲宽度。
  12. 一种基于交流电机控制电路的控制装置，其特征在于，所述基于交流电机控制电路的控制装置包括：
    获取模块，用于获取所述交流电机的目标转速；
    检测模块，用于检测所述交流电机控制电路输入电压的过零信号以及交流电机的实时转速反馈信号；
    控制模块，用于根据所述目标转速和实时转速反馈信号调整当前驱动脉冲信号的触发起始点，并控制当前驱动脉冲信号的结束点在所述的交流电流过零点时刻之后；其中，所述驱动脉冲信号以驱动所述交流电机运行达到目标转速。
  13. 如权利要求12所述基于交流电机控制电路的控制装置，其特征在于，所述控制模块还用于，
    根据所述目标转速和实时转速反馈信号调整当前驱动脉冲信号的触发起始点，且所述当前驱动脉冲信号的脉宽为预设的第一脉宽值，以使当前驱动脉冲信号的结束点在所述的交流电流过零点时刻之后。
  14. 如权利要求12所述基于交流电机控制电路的控制装置，其特征在于，所述控制模块还用于，
    判断所述的驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，控制所述驱动脉冲信号的结束点在交流电流过零点时刻之后。
  15. 如权利要求14所述基于交流电机控制电路的控制装置，其特征在于，所述控制模块还用于，
    判断所述的驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，获取本次交流输入电压周期对应的交流电流过零点时刻；
    调整当前驱动脉冲信号的脉冲宽度，以使所述驱动脉冲信号的结束点在所述的交流电流过零点时刻之后。
  16. 如权利要求14所述基于交流电机控制电路的控制装置，其特征在于，所述控制模块还用于，
    判断所述的驱动脉冲信号的触发起始点晚于本次交流输入电压周期对应的交流电流过零点时刻时，控制当前驱动脉冲信号的脉冲宽度为预设的第二脉冲宽度。
  17. 如权利要求14所述基于交流电机控制电路的控制装置，其特征在于，所述控制模块还用于，
    判断所述的驱动脉冲信号的触发起始点早于本次交流输入电压周期对应的交流电流过零点时刻时，控制当前驱动脉冲信号的脉冲宽度为预设的第三脉冲宽度，以使所述驱动脉冲信号的结束点在所述的交流电流过零点时刻之后。
  18. 如权利要求14所述基于交流电机控制电路的控制装置，其特征在于，所述控制模块还用于，
    判断所述的驱动脉冲信号的触发起始点晚于本次交流输入电压周期对应的交流电流过零点时刻时，控制当前驱动脉冲信号的脉冲宽度为预设的第四脉冲宽度，且所述第四脉冲宽度大于当前的脉冲信号的脉冲宽度。
  19. 一种空调器，其特征在于，所述空调器包括如权利要求12所述的控制装置。
PCT/CN2017/082516 2016-09-29 2017-04-28 一种交流电机控制方法、装置及空调器 Ceased WO2018058956A1 (zh)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
CN201610867829.0 2016-09-29
CN201610867829.0A CN106374807B (zh) 2016-09-29 2016-09-29 一种交流电机控制方法、装置及空调器

Publications (1)

Publication Number Publication Date
WO2018058956A1 true WO2018058956A1 (zh) 2018-04-05

Family

ID=57898301

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/CN2017/082516 Ceased WO2018058956A1 (zh) 2016-09-29 2017-04-28 一种交流电机控制方法、装置及空调器

Country Status (2)

Country Link
CN (1) CN106374807B (zh)
WO (1) WO2018058956A1 (zh)

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN111983300A (zh) * 2019-05-23 2020-11-24 深圳拓邦股份有限公司 电机电流检测方法、系统、搅拌机及存储介质

Families Citing this family (9)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN106374807B (zh) * 2016-09-29 2019-02-05 广东美的制冷设备有限公司 一种交流电机控制方法、装置及空调器
WO2019024227A1 (zh) * 2017-08-04 2019-02-07 广东美的生活电器制造有限公司 食物料理机及其恒速控制方法和装置
CN108551290B (zh) * 2018-03-30 2020-07-14 海信家电集团股份有限公司 一种pg电机控制电路、方法及设备
CN109286349A (zh) * 2018-06-28 2019-01-29 浙江绍兴苏泊尔生活电器有限公司 电机控制方法、电机控制电路及料理机
CN110410346B (zh) * 2019-07-23 2021-05-25 广东美的制冷设备有限公司 风机调速控制方法、系统及电器设备
CN110332139A (zh) * 2019-07-23 2019-10-15 广东美的制冷设备有限公司 风机调速控制方法、系统及电器设备
TWI716305B (zh) * 2020-03-30 2021-01-11 盛群半導體股份有限公司 脈衝訊號產生器
CN112803839B (zh) * 2020-12-31 2022-10-28 珠海格力电器股份有限公司 控制空调电机转速的方法及装置、存储介质和处理器
CN114123887A (zh) * 2021-09-30 2022-03-01 江苏华频电子科技有限公司 有刷电机的恒速控制方法和装置

Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN2814802Y (zh) * 2005-06-27 2006-09-06 广东科龙电器股份有限公司 一种空调器风扇电机无级调速装置
US7622880B1 (en) * 2006-10-13 2009-11-24 Marvell International Ltd. Voice-coil motor control with zero-current sensing
CN102185543A (zh) * 2010-07-15 2011-09-14 上海海洋大学 一种用于高压异步电动机的节能软起动装置
CN104579020A (zh) * 2013-10-25 2015-04-29 广东美的制冷设备有限公司 Pg调速电机的启动控制方法和启动控制系统
CN104848480A (zh) * 2015-04-30 2015-08-19 青岛海尔空调器有限总公司 空调器风机控制方法、控制装置及空调器
CN106374807A (zh) * 2016-09-29 2017-02-01 广东美的制冷设备有限公司 一种交流电机控制方法、装置及空调器

Family Cites Families (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN1043233A (zh) * 1988-12-10 1990-06-20 柳州市起重机厂 绕线式电动机起动和调速的方法及其装置
CN201674443U (zh) * 2010-05-21 2010-12-15 陶岗清 电机节能控制器
CN201904605U (zh) * 2010-11-30 2011-07-20 杨波 一种异步电动机自适应控制及保护系统
CN102832857B (zh) * 2012-08-16 2015-08-05 宁波大学 一种新型电机软起动器
CN103036501A (zh) * 2012-12-04 2013-04-10 中山市樱雪集团有限公司 一种燃气热水器上交流风机调速系统
CN103326662A (zh) * 2013-06-28 2013-09-25 华南理工大学 一种用于三相交流异步电动机的节能控制器及其控制方法

Patent Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN2814802Y (zh) * 2005-06-27 2006-09-06 广东科龙电器股份有限公司 一种空调器风扇电机无级调速装置
US7622880B1 (en) * 2006-10-13 2009-11-24 Marvell International Ltd. Voice-coil motor control with zero-current sensing
CN102185543A (zh) * 2010-07-15 2011-09-14 上海海洋大学 一种用于高压异步电动机的节能软起动装置
CN104579020A (zh) * 2013-10-25 2015-04-29 广东美的制冷设备有限公司 Pg调速电机的启动控制方法和启动控制系统
CN104848480A (zh) * 2015-04-30 2015-08-19 青岛海尔空调器有限总公司 空调器风机控制方法、控制装置及空调器
CN106374807A (zh) * 2016-09-29 2017-02-01 广东美的制冷设备有限公司 一种交流电机控制方法、装置及空调器

Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN111983300A (zh) * 2019-05-23 2020-11-24 深圳拓邦股份有限公司 电机电流检测方法、系统、搅拌机及存储介质
CN111983300B (zh) * 2019-05-23 2023-10-03 深圳拓邦股份有限公司 电机电流检测方法、系统、搅拌机及存储介质

Also Published As

Publication number Publication date
CN106374807A (zh) 2017-02-01
CN106374807B (zh) 2019-02-05

Similar Documents

Publication Publication Date Title
WO2018058956A1 (zh) 一种交流电机控制方法、装置及空调器
WO2019051909A1 (zh) 空调器运行参数调整方法、空调器及计算机可读存储介质
WO2019051905A1 (zh) 空调器控制方法、空调器及计算机可读存储介质
WO2014194483A1 (zh) 头灯亮度可调的电子烟及其亮度调节方法
WO2016187998A1 (zh) 动态调整背光方法及装置
WO2018058826A1 (zh) 电视机节能待机快速开机的方法及装置
WO2015143859A1 (zh) 光伏空调器的温度调节方法和系统
WO2017088427A1 (zh) 音频输出控制方法及装置
WO2015149562A1 (zh) 空调器及其压缩机保护电路
WO2015058455A1 (zh) 空调器及其控制方法、控制终端
WO2016058258A1 (zh) 终端远程控制方法和系统
WO2017107378A1 (zh) 基于hls流媒体的视频数据加速下载方法及装置
WO2019051902A1 (zh) 终端控制方法、空调器及计算机可读存储介质
WO2017219485A1 (zh) 智能电视及其控制方法
WO2018126888A1 (zh) 电视功能的快捷启动设置方法及装置
WO2019051900A1 (zh) 智能家居设备的控制方法、装置及可读存储介质
WO2019062113A1 (zh) 家电设备的控制方法、装置、家电设备及可读存储介质
WO2019169717A1 (zh) 空调器及其的控制方法和计算机可读存储介质
WO2018028124A1 (zh) 电视机及其信号源的切换方法
WO2017121066A1 (zh) 应用程序显示方法和系统
WO2019051903A1 (zh) 终端控制方法、装置及计算机可读存储介质
WO2017201943A1 (zh) 显示屏驱动方法及装置
WO2019068241A1 (zh) 空气处理系统及其控制方法、装置及计算机可读存储介质
WO2019051897A1 (zh) 终端运行参数调整方法、装置及计算机可读存储介质
WO2016101252A1 (zh) 智能电视的频道信息显示方法及装置

Legal Events

Date Code Title Description
121 Ep: the epo has been informed by wipo that ep was designated in this application

Ref document number: 17854414

Country of ref document: EP

Kind code of ref document: A1

NENP Non-entry into the national phase

Ref country code: DE

122 Ep: pct application non-entry in european phase

Ref document number: 17854414

Country of ref document: EP

Kind code of ref document: A1