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WO2015069035A1 - Procédé et dispositif d'émission et de réception de signal à l'aide de faisceaux multiples dans un système de communication sans fil - Google Patents

Procédé et dispositif d'émission et de réception de signal à l'aide de faisceaux multiples dans un système de communication sans fil Download PDF

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Publication number
WO2015069035A1
WO2015069035A1 PCT/KR2014/010611 KR2014010611W WO2015069035A1 WO 2015069035 A1 WO2015069035 A1 WO 2015069035A1 KR 2014010611 W KR2014010611 W KR 2014010611W WO 2015069035 A1 WO2015069035 A1 WO 2015069035A1
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Prior art keywords
beams
modulation frequency
equation
modulation
frequency
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English (en)
Korean (ko)
Inventor
최상혁
김용훈
양희성
전주환
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Samsung Electronics Co Ltd
Korea Advanced Institute of Science and Technology KAIST
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Samsung Electronics Co Ltd
Korea Advanced Institute of Science and Technology KAIST
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Priority to US15/035,201 priority Critical patent/US10389023B2/en
Publication of WO2015069035A1 publication Critical patent/WO2015069035A1/fr
Anticipated expiration legal-status Critical
Ceased legal-status Critical Current

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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/08—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
    • H01Q3/30—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array
    • H01Q3/34—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array by electrical means
    • H01Q3/36—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array by electrical means with variable phase-shifters
    • H01Q3/38—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array by electrical means with variable phase-shifters the phase-shifters being digital
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/0408—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas using two or more beams, i.e. beam diversity
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S19/00—Satellite radio beacon positioning systems; Determining position, velocity or attitude using signals transmitted by such systems
    • G01S19/01—Satellite radio beacon positioning systems transmitting time-stamped messages, e.g. GPS [Global Positioning System], GLONASS [Global Orbiting Navigation Satellite System] or GALILEO
    • G01S19/13—Receivers
    • G01S19/35—Constructional details or hardware or software details of the signal processing chain
    • G01S19/36—Constructional details or hardware or software details of the signal processing chain relating to the receiver frond end
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
    • H01Q3/30—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array
    • H01Q3/34—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array by electrical means
    • H01Q3/36—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array by electrical means with variable phase-shifters

Definitions

  • the present disclosure relates to a method and apparatus for transmitting and receiving signals using multiple beams in a wireless communication system.
  • BDMA beam division multiple access
  • carrier frequencies used by major domestic carriers are about 2Ghz band.
  • the hardware constituting the communication system is configured on the assumption of a narrow band system.
  • a narrow band system generally uses a bandwidth of 1/8 to 1/10 of the system carrier frequency.
  • Based on the 2GHz carrier frequency it uses a maximum bandwidth of about 200Mhz.
  • 2GHz carrier frequency it uses a maximum bandwidth of about 200Mhz.
  • carrier frequencies in the 28 to 30 GHz band which is 10 times higher than the current carrier frequency band, is being conducted.
  • the received power is proportional to the square of the wavelength and inversely proportional to the square of the distance. Therefore, when the carrier frequency is increased by 10 times, the wavelength of the carrier is reduced to 1/10, so that the received power is reduced to 1/100 based on the same distance. As a result, the use of this high-band carrier results in severe signal attenuation at the receiver. In order to overcome such signal attenuation, it is possible to reduce the size of the base station cell and to perform communication by generating a beam that maximizes SNR when transmitting and receiving a signal between the base station and the terminal.
  • the terminal must find a base station that maximizes SRN among a plurality of base stations that are much denser than a conventional communication system, find a beam that maximizes the SNR with the base station, and perform communication with the base station using the beam.
  • an embodiment of the present disclosure provides a method and apparatus for transmitting and receiving signals using multiple beams in a wireless communication system.
  • One embodiment of the present disclosure provides a method and apparatus for generating or receiving a plurality of multi-beams using one beam former in an antenna system supporting one multi-beam.
  • An embodiment of the present disclosure provides an antenna apparatus and an operation method capable of simultaneously obtaining a plurality of beam responses using one receiver in a multi-antenna system using an array antenna element.
  • a method of receiving a signal using M multiple beams includes: modulation for beam modulation of the M beams and frequency modulation of beam response; Setting a frequency for each M beams, generating the M beams according to the beam direction and modulation frequency set for each beam, and M beam responses to a received signal using the generated M beams Generating a signal, frequency modulating the generated M beam responses using a modulation frequency set for each beam, and performing band pass filtering on the frequency-modulated M beam responses, and separating the M beam responses by the M beam responses. And demodulating the separated M beam responses, respectively.
  • the setting of the beam direction and the modulation frequency may include a sum of a value obtained by multiplying the modulation frequencies for each beam by each of the M beams set in the k-th antenna element, to a transmission / reception module (TRM) connected to the k-th antenna element. Determining a beam direction and modulation frequency pairs to be one of the complex gain values that can be represented by, and selecting a beam direction and a modulation frequency for each of the M beams from among the determined beam direction and modulation frequency pairs.
  • the determining of the beam direction and modulation frequency pairs may include: converting a sum of a product of the M beams by a modulation frequency for each beam into a complex number having a magnitude and a phase;
  • the phase may be a multiple of a phase value that can be represented by a phase shifter in the TRM, and the converted magnitude may be represented by an attenuator in the TRM.
  • phase values in groups to express the phase shift is a 2 ⁇ X (1/2) Np, where Np is the number of bit phase shifter, a phase value by which the attenuator can be expressed is 2 ⁇ X (1/2) and Na Where Na is the number of bits of the phase shifter.
  • the method may further include storing the determined beam direction and modulation frequency pairs in a table form.
  • the sum of the values obtained by multiplying the modulation frequencies for each beam by the M beams is a value that changes with time.
  • an apparatus for receiving signals using M multiple beams may perform beam modulation and beam frequency modulation on the M beams.
  • a beam controller configured to set a modulation frequency for each M beams, a beam shaper for generating the M beams according to a beam direction and a modulation frequency set for each beam, and a received signal using the generated M beams
  • a receiver for generating M beam responses, and frequency-modulating the generated M beam responses using a modulation frequency set for each beam, and performing band pass filtering on the frequency-modulated M beam responses for each M beam responses.
  • a demodulation unit for demodulating each of the separated M beam responses.
  • FIG. 1 illustrates a receiver generally used to select a beam
  • FIG. 2 is a diagram illustrating a general receiver 200 for simultaneously obtaining a plurality of beam responses.
  • FIG. 3 is a view for explaining the structure of the TRM of FIG.
  • FIG. 4 is a diagram illustrating complex gain values that can be generated by using a phase shifter and an attenuator in the TRM of FIG.
  • FIG. 5 is a diagram illustrating signal reception when a plurality of TRMs are connected to one antenna element and a plurality of TRMs share one receiver;
  • FIG. 6 is a diagram illustrating a frequency response after frequency modulation of two beam responses according to modulation frequencies f1 and f2 according to an embodiment of the present disclosure
  • FIG. 7 is a diagram illustrating a result of filtering a frequency response signal frequency modulated by f1 and f2 using a band pass filter according to an embodiment of the present disclosure
  • FIG. 8 is a diagram illustrating a receiver for generating a plurality of beams using one beam former according to an embodiment of the present disclosure
  • FIG. 9 illustrates a method of generating a plurality of beams using one beam former and receiving a signal using the generated plurality of beams according to an embodiment of the present disclosure.
  • a basic concept of an embodiment of the present disclosure proposes a method and apparatus capable of simultaneously acquiring a response of a beam received from several directions using a single beam former in a multiple antenna system including a plurality of antenna elements.
  • 1 is a diagram illustrating a receiver generally used to select a beam.
  • FIG. 1 it is assumed that array antennas 101 are typically used, and the receiver 100 of FIG. 1 connects the receivers 103 to each of the array antennas 101 to digitally store response values of all array antennas.
  • the signal processor 105 digitizes the digital signal.
  • the receivers 103 are connected to every array antenna, the cost is very high. Therefore, in practice, a “sub array” antenna that connects one receiver to a plurality of array antenna elements is frequently used. In general, when multiple antennas are used, responses of an array antenna may be obtained through various algorithms such as adaptive processing. However, in the case of a low-cost receiver having one receiver, adaptive processing is not possible.
  • the next generation Wireless Personal Area Networks (WPAN) standard uses a simple method called "beam sweeping" to find transmit and receive beams.
  • the beam sweeping method has a disadvantage in that it takes much time for searching for the beam.
  • FIG. 2 is a diagram illustrating a general receiver 200 for simultaneously obtaining a plurality of beam responses.
  • the most basic method of acquiring a plurality of beam responses is to generate beams using the Transmit / Receive Module (TRM) 203 as many as the number of beams, and connect them to the array antenna 201 to transmit the respective TRMs. Steering the beam of the antenna element according to the beam direction set in accordance with (203), and is connected to the receivers 207 to the rear end of the TRMs 203, respectively, to obtain a response of the beam.
  • a system such as FIG. 2 is called a "beam space array antenna system”.
  • FIG. 3 is a view for explaining the structure of the TRM of FIG.
  • the TRM 300 includes a phase shifter 303 and an attenuator 301, which multiply each array antenna element by a complex beam gain for steering the beam. Function
  • the attenuator 301 takes charge of the magnitude of the complex gain and changes it to a size corresponding to the set complex gain.
  • the phase shifter 303 takes charge of the phase of the set complex gain and changes the phase to a phase corresponding to the set complex gain.
  • the TRM 300 includes a switch 305 for performing switching when transmitting and receiving a signal, a transmission function unit including a driver 309 and a power amplifier 311, and a low noise amplifier (LNA) 307 for receiving a signal. And a switch 313 for connecting the transmitting side signal chain and the receiving side signal chain with the antenna, respectively, during signal transmission and reception.
  • LNA low noise amplifier
  • FIG. 4 is a diagram illustrating values of complex gains that may be generated by using a phase shifter and an attenuator in the TRM of FIG. 3.
  • the small circles in FIG. 4 represent complex gain values that the TRM can generate using a phase shifter and an attenuator.
  • the number of complex gain values obtained by using a phase shifter and an attenuator is limited. The reason for such a complex gain is as follows.
  • Phase shifter 303 and attenuator 301 are designed to have specific bits.
  • attenuators designed with N bits are usually assigned 0.5 dB to the least significant bit (LSB), starting from the next bit, 2 0 , 2 1 , 2 2 ,. , It is designed to attenuate the 2 N-2 dB up to 2 N-1 - is generally designed to attenuate by 0.5 dB.
  • the minimum phase that the phase shifter can represent is ⁇ 2 ⁇ X (1 / N)>, and thus the phase shifter is an integer multiple of the minimum phase ⁇ 2 ⁇ X (1 / N)>. It is designed to increase the phase. Therefore, the number of complex gain values that can be generated by the phase shifter 303 and the attenuator 301 is limited as shown in FIG.
  • the wavelength of the signal is 1 cm.
  • the spacing of array elements is usually determined by half the wavelength. In this case, the spacing of the array elements is 5 mm.
  • the conducting wires connected to each array element are divided again by the number of beams and connected to each TRM.
  • the terminal uses a beam sweeping technique using only one TRM and one receiver, and even if the base station measures several beam responses in a beam space array structure, implementation costs arise.
  • the base station is expected to use an array antenna of at least 1 meter or more, and since 200 array elements are arranged per meter, the method of connecting the receivers to each array element requires about 200 receivers, and the implementation cost is considerable.
  • hundreds of array elements must be connected to thousands of TRMs and connected to each receiver, so that labor costs, coupling problems between conductors, and the cost of using multiple receivers are increased.
  • Embodiments of the present disclosure operate a beam in a manner different from the conventional method in a communication system using a plurality of beams.
  • a complex gain value calculated by precomputing a complex gain value that is optimally determined for each antenna for a target direction or an arbitrary channel. Or use the calculated complex gain value after calculating the complex gain value through adaptive processing. Also, since the direction or channel of the signal does not change during transmission or reception of the signal, it is common to use a fixed beam without changing the complex gain value for forming the beam.
  • a complex gain value according to time This changing "time varying beam weight" scheme is used. That is, by changing the complex gain value for the beam while transmitting and receiving a signal, the resultant value which is frequency-modulated by the beam-specific response and output through one receiver is moved to a specific frequency band instead of simply adding the beam-specific responses. shift), so that the beam-specific responses can be separated in the digital processing of the signal.
  • a sum of values obtained by multiplying M beams of arbitrary array antenna elements by respective modulation frequencies is converted into a complex form expressed in magnitude and phase.
  • the beam direction and modulation frequency pairs are determined to be one of the complex gain values obtained by the phase shifter and attenuator shown in Fig. 4.
  • the sum of the values obtained by multiplying the M beams by the modulation frequency sets a “complex gain value condition” to be the complex gain value of FIG. 4.
  • the complex gain value condition may be divided into a "phase condition” and a "size condition".
  • the phase condition is that when the sum of the M beams multiplied by respective modulation frequencies is expressed in magnitude and phase, each of the magnitude and phase satisfies a multiple of magnitude and phase that can be represented by the complex gain values of FIG. 4. will be.
  • a linear equation can be obtained from the phase condition and the magnitude condition. Substituting an arbitrary value into a setting parameter included in the linear equation yields a plurality of ⁇ beam direction, modulation frequency ⁇ values satisfying the complex gain condition. Can be.
  • the phase of the phase shifter and the level of the attenuator are adjusted according to the selected ⁇ beam direction, modulation frequency ⁇ , a plurality of beam formers are used. It can produce the effect of generating the beam at the same time.
  • the selected beam direction and the modulation frequency are fixed after being selected, in the embodiment of the present disclosure, since the complex gain value of the TRM connected to any antenna element is set to change with time, the TRM may be configured accordingly.
  • the phase of the phase shifter and the level of the attenuator are also continuously adjusted over time. However, the complex gain value of the TRM which changes with time will be in the range of the complex gain value shown in FIG.
  • an embodiment of the present disclosure assumes a communication system using a band limited signal such as OFDM.
  • the operation of the transmitter and the operation of the receiver are reciprocal, and for convenience, the operation of the receiver will be described below.
  • a "beam” radiates a signal so that a power of a transmission signal is maximized in a subspace of a specific direction or channel, or a signal of a received signal reaching a specific direction or a specific channel subspace. This means multiplying each antenna element with a complex gain in order to maximize power and receive a signal.
  • the "beam response" refers to a value obtained by obtaining a weighted sum of a received signal received from a plurality of antenna elements using a beam weight value specifically set.
  • One beam former means that one TRM is connected to each of a plurality of N antenna elements, and each TRM shares one receiver.
  • An embodiment of the present disclosure is for generating a plurality of beams (M) using one beam former in a receiving system including a plurality of antenna elements (N).
  • a transmission system according to an embodiment of the present disclosure may also be implemented corresponding to the receiving system.
  • the conventional receiving system described in FIG. 2 differs in forming three beams using three beam formers.
  • FIG. 5 is a diagram illustrating signal reception when a plurality of TRMs are connected to one antenna element and a plurality of TRMs share one receiver.
  • one receiver 500 includes four antenna elements 501-1 to 501-4, and it is desired to restore a received signal using two beams (first beam and second beam).
  • two TRMs are connected to each antenna element so that the beam weight of the first beam and the beam weight of the second beam will be multiplied by the received signal input to each antenna element.
  • two TRMs 503-1 and 504-1 are connected to the antenna element 501-1.
  • the TRM is connected to other antenna elements in the same manner.
  • the four beam weights constituting the first beam are multiplied by respective antenna elements 501-1 to 501-4 using four TRMs 503-1 to 503-4, and configure a second beam.
  • the received signal value through the four antenna elements (501-1 ⁇ 501-4) in FIG. Assuming that the signals are input in this order, the first beam has four beam weights (i.e., complex gain values). If it is set to have the first beam ( ), The beam response is given by Equation 1 below.
  • the weight value of the second beam If it is set to, the beam response value by the second beam becomes Equation 2 below.
  • the overall beam response of the receiver 505 may be the sum of the first beam response and the second beam response.
  • one beam former has been defined as "one TRM is connected to each of a plurality of antenna elements, and each TRM shares one receiver.” Accordingly, in FIG. 5, four TRMs 503-1 to 503-4 and the receiver 505 for the first beam become one beam former, and four RMs 504-1 to 504 for the second beam. -4) becomes another beam former.
  • the final output obtained by the receiver 505 is the beam response value (+2) of the first beam and the beam response of the second beam. It will be “0” which is the sum of the values (-2).
  • the two beam responses may be recovered from the sum of the two signal modulated signals.
  • the received signal input to the four antenna elements 501-1 to 501-4 is a signal modulated by the transmitter.
  • the analog beam former is composed of analog elements, there is a limit in the method of signal modulation that can use them.
  • the embodiment of the present disclosure assumes signal modulation using OFDM when transmitting and receiving signals, and OFDM modulation has a property of being band-limited.
  • a band-limited signal can be modulated using an analog device alone. Therefore, in the embodiment of the present disclosure, a frequency modulation method is used when modulating a signal for a beam response.
  • the signal modulation scheme is not limited to the frequency modulation scheme and may be used as long as the modulation scheme is possible using an analog device.
  • Receiving signal Suppose is input to four antenna elements 501-1 to 501-4.
  • p (t) is an OFDM signal transmitted from a transmitter, and the reason why p (t) is assumed is that the embodiment of the present disclosure assumes OFDM signal transmission and reception as described above.
  • the values (1, 2, 3, 4) multiplied by p (t) are channel gain values. As the OFDM signal p (t) passes through the channel, the channel gain values are multiplied by the OFDM signal p (t), and the values are input to the four antenna elements 501-1 through 501-4.
  • f1 is a modulation frequency for frequency modulation the beam response.
  • the beam response value of the first beam is represented by Equation 3 below.
  • Equation 4 the beam response of the second beam is expressed by Equation 4 below.
  • the output value of the receiving unit 505 is the sum of ⁇ Equation 3> and ⁇ Equation 4>, the result is the following equation (5).
  • Equation 5 can be seen that the signal component including the modulation frequency f1 and the signal component including the modulation frequency f2.
  • Equation 5 when two signal components constituting Equation 5 are processed through digital signal processing (FFT), two spectra of p (t), which are transmission signals, appear as starting points of frequencies f1 and f2.
  • FFT digital signal processing
  • FIG. 6 illustrates a frequency response after frequency modulation of two beam responses according to modulation frequencies f1 and f2 according to an embodiment of the present disclosure.
  • the frequency response signal of FIG. 6 may be separated into signals starting with the frequencies f1 and f2 through a band pass filter.
  • FIG. 7 is a diagram illustrating a result of filtering a frequency response signal modulated by f1 and f2 using a band pass filter according to an exemplary embodiment of the present disclosure.
  • two signals are separated into respective signals having f1 and f2 as starting points after the band pass filtering.
  • the original received signal can be recovered.
  • the gain value multiplied by the original received signal is the response by the first beam and the second beam. Therefore, the beam response can be known through this process.
  • the beam responses may be separated by frequency modulating the beam responses.
  • FIG. 8 is a diagram illustrating a receiver for generating a plurality of beams using one beam former according to an embodiment of the present disclosure.
  • the receiver 800 of FIG. 8 Comparing the receiver 800 of FIG. 8 with the receiver 500 of FIG. 5, there is a difference in that it includes only one beam former. That is, four TRMs 503-1, 503-2, 503-3, and 503-4 and one receiver 505 configure one beam former.
  • a beam controller 807 may be included, and the storage unit 809 may be further included.
  • the beam controller 807 determines ⁇ beam direction, modulation frequency ⁇ pairs for each of the plurality of beams to generate the plurality of beams. At this time, when determining ⁇ beam direction, modulation frequency ⁇ , the sum of values obtained by multiplying the modulation frequencies by M beams for an arbitrary array antenna element is a complex gain obtained by the phase shifter and the attenuator shown in FIG. Determine the beam direction and modulation frequency pairs to be one of the values.
  • the receiver 505 obtains a beam response by the plurality of beams, and transmits the beam response to the digital signal processor 811.
  • the digital signal processor 811 receives ⁇ beam direction, modulation frequency ⁇ information from the beam controller 807, performs frequency modulation on the M beams using the modulation frequency according to the information, and performs frequency modulation on the beam.
  • Band pass filter the responses. Since the frequency modulation and band pass filtering have been described with reference to FIGS. 6 and 7, a detailed description thereof will be omitted.
  • the demodulator 813 can demodulate the band response filtered and separated beam responses to obtain the separated beam response.
  • the condition for the sum of the M beams multiplied by the modulation frequency to be the complex gain value of FIG. 4 will be referred to as a "complex gain value condition".
  • the " complex gain value condition &quot can be divided into a " phase condition " and a " size condition ", and a method of determining a ⁇ beam direction, modulation frequency ⁇ pair that satisfies these conditions will be described later.
  • ⁇ beam direction, modulation frequency ⁇ pairs satisfying the complex gain value condition for each beam direction there may be a plurality of ⁇ beam direction, modulation frequency ⁇ pairs satisfying the complex gain value condition for each beam direction. Therefore, ⁇ beam direction, modulation frequency ⁇ that satisfies the complex gain value condition may be previously stored in the storage unit 909 in a table format, and the ⁇ beam direction, modulation frequency ⁇ pair to be used for the plurality of beams may be selected from this table. That is, when the beam is to be set in a specific direction, the ⁇ beam direction, modulation frequency ⁇ corresponding to the corresponding direction may be selected from a previously stored ⁇ beam direction, modulation frequency ⁇ table.
  • FIG. 9 is a diagram for describing a method of generating a plurality of beams using one beam shaper and receiving a signal using the generated plurality of beams according to an exemplary embodiment of the present disclosure.
  • the beam controller 807 sets (beam direction, modulation frequency) for each of the plurality of beams.
  • the beam controller 807 sets (beam direction, modulation frequency) for each of the plurality of beams.
  • the ⁇ beam direction, modulation frequency ⁇ values may be stored in a table form in advance in the storage unit 809, and one of the values stored in the table may be selected.
  • a plurality of beams are generated by controlling values of a phase shifter and an attenuator included in the TRMs connected to the beams according to (beam direction, modulation frequency) values of the plurality of beams.
  • the receiver 505 obtains a beam response based on the generated beams.
  • the receiver 505 performs frequency modulation on the beam response using the plurality of modulation frequency values with respect to the obtained beam response.
  • each of the frequency-modulated beam responses is band pass filtered. This separates the response for each beam.
  • step 911 frequency demodulation of the frequency-modulated signals separated by the band pass filtering is performed for each signal to obtain a plurality of beam responses.
  • steps 905 processes before step 905 are generally performed through analog signal processing, and operations below step 905 are generally performed through digital signal processing, but embodiments of the present disclosure are limited thereto. no.
  • the beam controller 807 determines a ⁇ beam direction, modulation frequency ⁇ pair that satisfies the "complex gain value condition" will be described.
  • the TRMs constituting the beamformer include a phase shifter and an attenuator, and the beam gain value of the corresponding antenna element is set using the phase shifter and the attenuator.
  • the complex gain values that can be generated using the phase shifter and the attenuator are limited to the complex gain values shown in FIG. 4. The following descriptions describe the process of finding the beam direction and modulation frequency that satisfy this complex gain value condition.
  • the reason for setting the beam direction and the modulation frequency for each antenna element in step 901 is as described above. That is, when a plurality of beams are simultaneously generated by one analog beam former, and each beam response according to the generated beams is frequency modulated, this is mathematically represented as the sum of complex numbers that change over time. This results in the sum of the complex numbers changing over time being one of the complex gain values shown in FIG. 4, and once a particular beam direction and modulation frequency is found that makes this possible, multiple beams can be simultaneously Will produce the result.
  • Equation 6 the complex gain values set for the antenna elements in the TRM are represented by Equation 6 below.
  • kd is a value obtained by multiplying a wavelength by an interval between antenna elements, and is typically set to be ⁇ .
  • Equation 7 when the beam b1 is multiplied by an arbitrary modulation frequency f1 set for frequency modulation, it is expressed by Equation 7 below.
  • the M beams are each frequency-modulated and then added to their values. It is represented by ⁇ Equation 8>. Where the M beam directions are ⁇ 1, ⁇ 2, .., ⁇ M, respectively, and the modulation frequencies are f1, f2,... , fM is assumed.
  • Equation 8 divides the number of beams M to normalize power
  • Equation 9 is obtained.
  • Equation 10 the complex gain that the TRM connected to the k-th antenna element should represent is expressed by Equation 10 below.
  • M beams may be generated using one analog beam former and a receiver. That is, in the embodiment of the present disclosure, M beams are generated for N antenna elements by using a beam former including one TRM and one receiver.
  • one analog beamformer connected to the N antenna elements simultaneously generates M beams, and frequency modulates each of the generated M beams.
  • Obtain beam directions and modulation frequencies such that the sum of the complex gain values of the plurality of beams becomes one of the complex gain values shown in FIG. 4, and determine the phase shifter and attenuator of the TRM according to the If adjusted, it is possible to obtain the effect that one TRM simultaneously generates a plurality of beams.
  • the magnitude of the complex gain values in FIG. 4 is difficult to find exactly mathematical regularity. Therefore, in the embodiment of the present disclosure, a condition is set such that the magnitude portion of the total complex value of Equation 10 is as close as possible to the magnitude portion of the complex gain values of FIG. 4. This will be described later, but the conclusion is that the magnitude portion of the total complex value of Equation 10 is a multiple of 2 ⁇ X (1/2) Np . This is the magnitude condition among the complex gain value conditions.
  • Np means the number of bits of the attenuator.
  • Equation 10 is a process of adding N complex numbers having a size of 1, where the values of the complex numbers vary with time t.
  • complex values constituting Equation 10 are digitized by an analog / digital converter. Therefore, in Equation 10, the equation 10 is modified in terms of discrete signals instead of t, which is a time continuous signal, so that Equation 10 satisfies the condition shown in FIG. 4 with respect to the discrete signals. And modulation frequencies can be found.
  • Equation 11 the magnitude and phase thereof may be represented, and the Euler format may be as shown in Equation 11 below.
  • a and b represent the magnitude and phase of each complex number.
  • each of the complex components constituting Equation 10 is converted into the Euler format, and the total sum of each of the complex components converted into the Euler format is also the Euler format. That is, when Equation 10 is converted into one Euler format, the phase portion of the complex number converted to the Euler format corresponds to the phase that the phase shifter is in charge of and the size portion corresponds to the size of the attenuator.
  • Equation 10 may be expressed as Equation 12 below.
  • Equation 12 expresses the sum of M beam responses with respect to the k-th antenna element as a discrete signal
  • Equations 13 to 16 describe the process of converting Equation 12 to Euler format.
  • Equation 13 the sum of two complex numbers having a size of 1 may be expressed in Equation 13 in Euler format.
  • Equation 14 the sum of the four complex numbers of size 1 may be expressed by Equation 14 below.
  • Equation 14 four Euler type complex numbers are expressed as the sum of two sub Euler types.
  • Equation 15 may be bundled into one Euler type using special conditions.
  • the special condition is that the final equation form is one Euler form.
  • the form of the final equation is expressed as the product of the phase part and the magnitude part.
  • Equation 12 is the sum of two Euler-type complex numbers, and in order to convert Equation 12 into one Euler-type complex number, the phase values of two Euler-type complex numbers of Equation 12 are converted. Substituting A and B in Equation 15 and arranging, Equation 12 becomes Equation 16 below.
  • the phase portion is the phase of the TRM connected to the k-th antenna that the phase shifter is responsible for
  • the magnitude portion is the TRM connected to the k-th antenna that the attenuator is responsible for. Size.
  • Equation 16 only the phase component is represented by Equation 17 below.
  • Equation 18 is obtained.
  • Equation 18 which is a phase component of Equation 16 may be used.
  • the phase shifters of this TRM It must be expressed in multiples of. This is the phase condition among the complex gain conditions according to the embodiment of the present disclosure.
  • Np is the number of bits of the phase shifter.
  • Equation 18 The sum of the two factors that make up Equation 18 In order to be expressed as a multiple of, the first component of Equation 18 And the second component argument Each of these It must be expressed as a multiple of. When formulated, the equations (19) and (20) are obtained.
  • I 1 and I 2 are integer values as design parameters.
  • Equation 20 is summarized with respect to frequencies f1 and f2 and directions sin ⁇ 1 and sin ⁇ 2, Equation 20 is expressed by Equation 21 below.
  • Equation 21 is expressed by Equation 22 below.
  • Equation 22 shows that the sum of the complex gain values of the two beams for the k-th antenna element is shown in FIG. 4 in order to generate two beams using one analog beam former. A phase condition that results in one of the complex gain values.
  • the size portion is in charge of the attenuator of the TRM.
  • Equation 23 is obtained.
  • Equation 23 has a structure in which it is difficult to completely match a grid of an attenuator generally used in TRM.
  • Equation 23 an attenuation level value corresponding to the magnitude value of the complex gain value shown in FIG. 4 may be generated.
  • a new type of attenuator of distortion type disortion type
  • the distortion type attenuator can be supported.
  • the integer numbers changing in Equation 23 are l and k.
  • the arguments in the cosine function included in Equation 23 should have periodic values.
  • the values of the factors inside the cosine function are multiples of 2 ⁇ X (1/2) Na similarly to the values previously used in the phase. Na represents the number of bits of the attenuator
  • Equation 24 is obtained.
  • Equation 25 In a manner similar to that described in Equation 18 regarding the phase shifter, in order to have a periodic value according to l and k in which the sum of two factors in Equation 25 changes, Equation 25 The first and second arguments of the> must satisfy Equations 26 and 27, respectively.
  • I 3 , I 4 are determined experimentally as integer values which are arbitrary design parameters.
  • Na the number of bits attenuator will have.
  • Equation 27 is summarized into equations for frequencies f1 and f2 and directions sin ⁇ 1 and sin ⁇ 2, Equation 28 can be obtained.
  • Equation 28 is expressed by Equation 29 below.
  • Equation 29 shows that the sum of the complex gain values of the two beams for the k-th antenna element is shown in FIG. 4 in order to generate two beams using one analog beam former. It is a magnitude condition that makes it one of the complex gain values.
  • Equation 22 is an equation generated from a phase condition for generating two beams using one analog beam former
  • Equation 29 is an equation generated from a magnitude condition.
  • Both conditional equations are linear equations for the beam direction (sin ⁇ 1, sin ⁇ 2) and the modulation frequencies f1, f2, Is a value determined experimentally as a design parameter.
  • Equation 32 the sum of the above-described phase conditional equation for the phase shifter (Equation 22) and the magnitude conditional expression for the attenuator (Equation 29) together, and write again as ⁇ Equation 30> and ⁇ Equation 31>, If two equations are expressed as linear equations, the following Equation 32 can be obtained.
  • Equation 32 Is any value as a design parameter. That is, the above Equation (32)
  • the values of ⁇ beam direction ( ⁇ 1, ⁇ 2) and frequency (f1, f2) ⁇ pairs are determined. At this time Can substitute any value, so the number of combinations of ⁇ beam directions ⁇ 1 and ⁇ 2 and frequencies f1 and f2 ⁇ will be very large. Therefore, when a plurality of ⁇ beam direction ⁇ 1, ⁇ 2) and frequencies (f1, f2) ⁇ values are stored in advance in a table format and a signal is to be received using the beam, the number of beams required in the stored table corresponds to The signal may be received by obtaining a beam direction and a modulation frequency pair.
  • Table 1 is an example for clarity. In other words, Is substituted into Equation 31, a solution of a pair of ⁇ beam directions ⁇ 1, ⁇ 2, frequencies f1, f2 ⁇ is determined, as shown in Table 1 from the solution of a large number of linear equations. Corresponding modulation frequency pairs will be found for the two beam direction pairs. In addition, in Table 1, modulation frequency pairs are illustrated as a total of six pairs for beam direction pairs ⁇ 1 and ⁇ 2 ⁇ , and beam direction pairs are illustrated as a total of 11 pairs for beam direction pairs ⁇ 3 and ⁇ 4 ⁇ . Of course, the number of modulation frequency pairs corresponding to may vary.
  • the frequency for the corresponding beam direction pair Selecting one of the pair values and adjusting the phase and magnitude values of the TRM according to the beam direction pair and the frequency pair will result in the generation of multiple beams simultaneously using one analog beam former.
  • the basic method is the same as the case where the number of beams is two. That is, when using four beams for the N antenna elements, the complex gain for any k th antenna element is expressed in Euler format, and the phase and magnitude portions of the complex gain values expressed in Euler format are shown in FIG. It is to find a direction and modulation frequency pair corresponding to a condition that is expressed by one of phase values and magnitude values of the complex gain value shown in FIG.
  • the first method assumes that the phase portions of each of the two Euler types of complex numbers are the same, and the second method assumes that the size parts of the complex numbers of each Euler type are the same.
  • Equation 34 the conditional expression of Equation 34 can be obtained.
  • Equation 34 the Euler type of Equation 35 below can be obtained from Equation 33.
  • Equation 35 The part is a part which the phase shifter should be in charge of, and in Equation 35 The part is the part that the attenuator should be in charge of.
  • Equation 35 In a second method, assuming that the size portion of each of the two complex numbers in Equation 32 is the same, the conditional expression of Equation 35 can be obtained.
  • Equation 35 may be expressed in an Euler form of Equation 37 below.
  • Equation 37 the phase portion Is the part that the phase shifter should be responsible for. In the same manner as in the embodiment assuming two beams, an equation including any setting parameter can be obtained.
  • the modulation frequency and the beam direction for each beam may be obtained in the same manner.
  • the signal for the corresponding ⁇ (beam direction pair), (modulation frequency pair) ⁇ is transmitted from the beam controller 807. It is delivered to the phase shifter and attenuator of the TRM. Thereafter, the phase shifter and the attenuator continuously change its bits according to the sampling time to perform frequency modulation of beam steering and beam-specific responses as the time changes.
  • Equation 10 Assuming two beams, the beam directions ⁇ 1, ⁇ 2 ⁇ and modulation frequencies f1, f2 are already determined and fixed in Equation 10, and k is also a fixed value. Therefore, in Equation 10, only time t becomes a variable. Since t changes in units of the bit sampling time (ts), the overall complex gain value also changes. Therefore, in order to implement W (k), the phase shifter and the attenuator must switch the bits of the phase shifter and the bits of the attenuator according to the sampling time. This is because W (k) can be one of the complex gain values shown in FIG.
  • the TRM uses a fixed complex gain value
  • the bits of the phase shifter and the attenuator do not have to be switched according to the sampling time.
  • a plurality of beams are simultaneously generated by one analog beam former.
  • W (k) changes over time with one of the complex gain values of FIG. 4. Therefore, in the embodiment of the present disclosure, since the total complex gain value by the plurality of beams for the k-th antenna element changes in time, it is necessary to change the bits of the phase shifter and the attenuator according to the complex gain value that changes in time.
  • the digitized output signal at the receiver can be separated separately through a band pass filter. This is as described in FIG. 6.
  • the beam-specific response separated by the band pass filter is a state in which the j j pi part is multiplied by the frequency modulation. Therefore, by multiplying and demodulating the e -j2 ⁇ ft part, a response for each beam can be obtained.
  • a complex gain value for forming a beam during signal transmission and reception using time-varying beam weights is obtained.
  • the output of one receiver is moved to a specific frequency band, so that the response of each beam can be separated in the digital processing of the signal. This reduces the manufacturing cost of the terminal and enables the adaptive processing using the digital signal processing (DSP) of the plurality of beam responses to reduce the time required to find the optimal beam.
  • DSP digital signal processing
  • embodiments of the present disclosure may be applied to various fields that receive and utilize a plurality of beam responses.
  • it can be applied to the WiGig dedicated terminal using the beam as a medium to reduce the time for the beam sweeping.
  • the radar may be introduced into a monopulse antenna that tracks the direction of the target to increase the degree of freedom of adaptive processing.
  • it is applied to a terminal of BDMA, which is one of the next generation communication technologies, and has many advantages when compared to a terminal having one RF chain.
  • the time for selecting the optimal beam is faster when handovers between base stations. Therefore, the discovery, handover initiation, and network re-entry processes of neighboring base stations are also performed. It can be performed quickly, enabling seamless handover.

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  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Radio Transmission System (AREA)
  • Variable-Direction Aerials And Aerial Arrays (AREA)

Abstract

La présente invention, selon un mode de réalisation, concerne un procédé de réception d'un signal à l'aide de M faisceaux multiples d'un système à antennes multiples comprenant N éléments d'antenne, comprenant les étapes consistant à : définir, à l'aide de M faisceaux, une direction de faisceau des M faisceaux et une fréquence de modulation de modulation de fréquence d'une réponse de faisceau ; générer les M faisceaux conformément à la direction de faisceau et à la fréquence de modulation définies par les faisceaux ; générer des réponses de M faisceaux d'un signal de réception à l'aide des M faisceaux générés ; moduler en fréquence les réponses des M faisceaux générés à l'aide de la fréquence de modulation définie par les faisceaux ; faire subir un filtrage passe-bas aux réponses modulées en fréquence des M faisceaux de façon à séparer les réponses des M faisceaux ; et démoduler respectivement les réponses séparées des M faisceaux.
PCT/KR2014/010611 2013-11-06 2014-11-06 Procédé et dispositif d'émission et de réception de signal à l'aide de faisceaux multiples dans un système de communication sans fil Ceased WO2015069035A1 (fr)

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WO2020101640A1 (fr) * 2018-11-12 2020-05-22 Nokia Technologies Oy Amélioration de résolutions de direction de faisceau
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