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WO2012061999A1 - Système de commande de courant d'éclairage à del (diodes électroluminescentes) à réactance - Google Patents

Système de commande de courant d'éclairage à del (diodes électroluminescentes) à réactance Download PDF

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Publication number
WO2012061999A1
WO2012061999A1 PCT/CN2010/078697 CN2010078697W WO2012061999A1 WO 2012061999 A1 WO2012061999 A1 WO 2012061999A1 CN 2010078697 W CN2010078697 W CN 2010078697W WO 2012061999 A1 WO2012061999 A1 WO 2012061999A1
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circuit
led
resistor
current
cathode
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Shan C Sun
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Individual
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Priority to PCT/CN2010/078697 priority Critical patent/WO2012061999A1/fr
Priority to CN201110364685.4A priority patent/CN102404917B/zh
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    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/40—Details of LED load circuits
    • H05B45/44—Details of LED load circuits with an active control inside an LED matrix
    • H05B45/48—Details of LED load circuits with an active control inside an LED matrix having LEDs organised in strings and incorporating parallel shunting devices
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/37—Converter circuits
    • H05B45/3725—Switched mode power supply [SMPS]
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/40—Details of LED load circuits
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/50—Circuit arrangements for operating light-emitting diodes [LED] responsive to malfunctions or undesirable behaviour of LEDs; responsive to LED life; Protective circuits
    • H05B45/54—Circuit arrangements for operating light-emitting diodes [LED] responsive to malfunctions or undesirable behaviour of LEDs; responsive to LED life; Protective circuits in a series array of LEDs
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/40—Details of LED load circuits
    • H05B45/44—Details of LED load circuits with an active control inside an LED matrix
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/50—Circuit arrangements for operating light-emitting diodes [LED] responsive to malfunctions or undesirable behaviour of LEDs; responsive to LED life; Protective circuits
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B20/00—Energy efficient lighting technologies, e.g. halogen lamps or gas discharge lamps
    • Y02B20/30—Semiconductor lamps, e.g. solid state lamps [SSL] light emitting diodes [LED] or organic LED [OLED]

Definitions

  • the present invention is in the field of LED lighting. More specifically it teaches a new method and related schemes to achieve efficient LED driver and control designs in all applications.
  • LED lighting drivers/power supplies invariably use the standard AC-to-DC conversion method, i.e., using an off-line rectification with a capacitive energy holding front-end circuit followed by a switching regulator which provides the required drive (either voltage or current) to the LED.
  • a design of this nature requires involved EMI (electro-magnetic interference) filtering to restrict bi-directional noise (both single-mode and common-mode) from entering the domains of the circuit and the AC line. Also additional circuit elements may also be required to protect the fragile on-board electronics against hostile power surge and ever-present power line and system disturbances. Therefore, a complete driver circuit using this concept may contain a large number of components in addition to the necessary switching regulator and the secondary side constant-voltage or constant-current generator. The heat generated by this drive circuit which is about 15 to 25% of the rated LED power, still adds to the temperature problem that is most critical in an LED light design.
  • Another prior art category uses a combination of a capacitor, rectifier diodes and a current limiting resistor to achieve the LED lighting drive.
  • the method is highly inefficient and has seldom been used in serious LED lighting applications.
  • the present invention was achieved to address not only the deficiencies of prior art LED driver designs, it also offers the ease and flexibility for applying LED lights to present-day incandescent light circuits and fixtures. As a result, a variety of driver and driver related functions/products have been contemplated and included as subsets of the present invention.
  • the present invention offers a novel concept that will drastically lower the cost and simplify the process and production of such applications in all vehicular LED applications.
  • the Reactance LED Lighting Current Driver scheme as known in the present invention delivers the exact LED light current from an AC voltage source. Moreover, it pushes the envelope reaching almost the theoretical limit for power efficiency; also, the leading power factor it could generate further enhances energy savings. With no inherent EMI (electro-magnetic interference) noise, the present invention is far more superior to any of the LED drivers known today.
  • the invention also includes and describes the following:
  • LED light bulb fabrication Incorporating the core circuit in bulb making using conventional socket base format (screw base for instance) allows the continuing use of existing sockets or receptacles for the LED lights. In this case the disclosed LED driver circuit is an integral part of the light bulb.
  • the light bulb will contain only the LED light source but it can be mated with existing sockets/receptacles. In this case the drive circuit will be a part of the light switch (wall-mount (fixed-mounting)) or otherwise.
  • LED dimmer circuits of multiple physical forms all using the disclosed reactance current generation design.
  • FIG. 1 shows a simplified schematic of an LED current driver circuit of the present invention for powering an LED load at a current defined by an reactance element
  • FIG. 2 shows a functional block diagram of the disclosed reactance LED current driver scheme. All essential elements and functional subsets are shown for reference;
  • FIG. 3 shows a simple LED current monitoring and current diversion circuit
  • FIG. 4 shows yet another simple LED over-current monitoring and protection circuit
  • FIG. 5 shows a more involved LED over-current monitoring and protection circuit
  • FIG. 6 shows yet another more involved LED monitoring and protection circuit
  • FIG. 7 shows another form of LED over-current monitoring and protection circuit
  • FIG. 8 shows yet another form of LED over-current monitoring and protection circuit
  • FIG. 9 shows examples of possible LED light bulb fabrication using an embodiment of the present invention.
  • FIG. 10 shows possible LED lights and light fixtures using the present invention
  • FIG.11 shows a functional diagram describing how the present invention can be segregated to produce more functional products
  • FIG. 12 shows a dimmer switch function using the present invention
  • FIG.13 shows a dimmer switch as a standalone product
  • FIG. 14 shows yet another design scheme for dimmer function using the present invention
  • FIG. 15 shows a practical design of the dimmer function using the concept described in FIG. 14;
  • FIG. 16 shows a digital implementation of the dimmer function also using the teaching illustrated in FIG. 14. Wireless remote addressing and control are also included in the scheme;
  • FIG. 16 also shows in block diagram form a digital implementation of the analog circuit shown FIG.15 with the adding of a wireless remote control and a digital control interface;
  • FIG. 17 shows how the present invention is contemplated for LED applications in the 400Hz AC power environment such as on-board an aircraft and other aviation, airborne and space-borne equipment;
  • FIG. 18 shows a break-through concept to provide simplified and lower application for LED light deployment in automobiles and vehicles
  • FIG. 19 shows a new technique for limiting and controlling the LED average current
  • FIG. 20 shows a practical implementation embodying the teaching in FIG. 19;
  • FIG. 21 shows an efficient design using the present invention to serialize the connection of multiple LED light using the capacitor generated current source
  • FIG. 22 shows a solar photo voltaic AC-LED solar emery collection, storage and DC-to-AC LED drive system.
  • the present invention describes an extremely simple, cost-effective, EMI-free and the most energy-efficient design that will allow the long-waited LED lighting revolution to take place.
  • the invention application areas are:
  • LED light bulb fabrication 1 Incorporating the invention in bulb making using conventional socket base format (screw base for instance) allows the continuing use of existing sockets or receptacles for the LED lights. In this case the disclosed LED driver circuit is an integral part of the light bulb.
  • LED light fabrication 2 The light bulb will contain only the LED light source but it can be mated with existing sockets/receptacles. In this case the drive circuit will be a part of the light switch (wall-mount (fixed-mounting)) or otherwise.
  • FIG. 1 A simplified circuit diagram shown in FIG. 1 describes the basic operation theory of the present invention.
  • the reactance element represented by Capacitor 103 and the rest of the circuit receives the AC voltage 100 through terminals 101 and 102.
  • Circuit elements 109, a MOV (metal oxide varistor) and a surge limiter 110 provide protection and conditioning of the AC voltage.
  • Capacitor/reactance 103 defines the current and feeds it to a rectifier bridge comprising diodes 104 through 107.
  • the rectified current labeled Iout flows from the junction of the cathodes of diodes 106 and 107 to power the LED light.
  • the electrical capacity of the reactance 103 is determined by the desired current, the AC voltage amplitude and frequency.
  • Circuit element 111 is a filter capacitor that further conditions the rectified current.
  • Reactance 103 according to the teaching of the present invention could also be an inductor, or a combination of both a capacitor and an inductor. It is, however, most practical to use just the capacitance to achieve the LED current generation. Being a reactive element, capacitor 103 will not consume real power, therefore, other than very little power loss in the rectifiers, the only power consumption is in the LED itself. This fact grants the present invention the highest possible energy efficiency for an LED driver circuit. Moreover, 103 being a capacitor also produces a leading power factor which in most of application environment would help improve the overall power efficiency. This is a significant benefit when the present invention is applied in large scale.
  • the AC power source is 120Volts, 60 Hz and the LED forward voltage drop is 20 Volts.
  • FIG.1 merely gives the theoretical base of one part of the present invention. More features and functions must be added to make the reactance current generation practical.
  • FIG.2 shows therefore a more complete circuit diagram.
  • a failure protection fuse or a small value resistor 202 is added in case a catastrophic Capacitor 103 failure occurs.
  • Added also is a resistor bleeder circuit 204 for maintenance and repair safety.
  • Resistor 206 also serves as a current bleeder. Not all of these elements are needed for every application.
  • Product formation and application environment dictate what features and to what extent these circuit elements are implemented.
  • One element, however, in the present invention most likely to be included in any embodiment is the LED excess current diversion circuit 207. This feature prevents the LED being harmed by unforeseen excess currents therefore ensures the LED longevity.
  • a practical design using the present invention may contain some or all the features as illustrated in FIG. 2.
  • the present invention receives the AC voltage 100 through terminals 101 and 102.
  • MOV 109 as an energy-absorber provides protection against abnormal input AC voltage with excessive peak amplitudes.
  • Element 202 is a fuse or a small-valued, low-wattage resistor providing protection against catastrophic failures anywhere in the circuit especially Capacitor 103.
  • Surge limiter 110 checks the current that flows in from element 202. During a power switching or load change, the AC voltage may contain frequency components substantially higher than the normal power frequency. The abnormal frequency currents must be effectively restricted from passing to capacitor 103. An inductor is a usual choice for 110 for this purpose.
  • a current diversion circuit comprising elements 208 and 207 provides excessive current protection for the LED.
  • Element 208 is a current monitor circuit. It may be placed anywhere in the Iout flow path. The output of current monitor 208 controls the current diverter 207. Both the current monitor 208 and diverter 207 are inert when the instantaneous value of Iout is within the normal range. However as soon as the upper limit of the range is exceeded, current monitor 208 will respond which in turn activates the current diverter/shunt circuit. This action will turn off the LED light thereby achieving the LED protection.
  • an inductor or a low-value resistor 209 may be opted and placed between the cathode-cathode junction of the bridge rectifier and capacitor 111 to provide more filter action for the design.
  • FIG. 3 a simple LED current monitoring and diversion circuit is shown. “Point “a”” and “Point “b”” are the take-off points from FIG. 2 where the LED and the associated protection elements 207 and 208 providing current monitoring and diversion are connected to.
  • FIG. 3 though functional and practical is presented to illustrate the principle of the LED current diversion principle. Note resistor 303 in the path to meter the LED current. When the current reaches a level that about 0.6V is produced across 303, excess current is diverted through transistor 301. Resistor 303 may be of a fast, high-gain transistor or FET of MOS (metal-oxide-semiconductor) kind. Resistor 302 regulates transistor 301 base current. The circuit in FIG.
  • FIG. 3 shows how Iout is monitored when it flows entirely in the path of the LED.
  • current measuring devices such as a Hall-effect kind could be used in lieu of resistor 303, a simple resistive element 303 is deemed sufficient.
  • using a bipolar transistor 301 base-to-emitter “on-voltage” for establishing the threshold is for its simplicity.
  • the current measuring device such as 303 may be placed anywhere in the LED current path. Resistor 303 placed in the LED cathode path as shown may also be placed in the anode path for achieving the same purpose.
  • FIG. 4 shows a simple transient/instantaneous current diversion circuit to illustrate a design principle.
  • capacitor 402 and resistor 403 form a frequency sensitive network that permit certain high frequency components to pass which in turn turns on transistor 401 achieving the diversion of harmful currents to reach the LED.
  • Resistors 405 and 406 set and regulate the operation of transistor 401.
  • This circuit may be included as a standalone element or to work with a circuit similar to the circuit shown in FIG. 3 to achieve a more complete protection for the LED in the present invention.
  • a MOSFET device may also be suited for 401 in lieu of the bipolar transistor as shown.
  • this circuit shows a more accurate and speedier LED protection circuit.
  • this circuit forms a base for other functionality to evolve under the teaching of the present invention.
  • Begins with “Point “a”” diode 515 segregate a power conditioning circuit 501 from Point “a”.
  • 501 is a 3-terminal regulator (5V to 30V or higher) whose output 503 designated V+++ is further derived through a resistor divider 506 to produce two lower reference voltages V++ 504 and V+ 505.
  • Capacitor 502 serves as filter/storage function for supply voltage V+++.
  • Resistor 514 measures the LED current serving the function similar to the current monitors in aforementioned circuits in FIG. 2 and FIG. 3.
  • Operational amplifier 511 is configured as a comparator circuit that receives the quantity of the LED current represented by the voltage Vm across resistor 514. Resistors 513, 510 and 512 form a hysteresis network that aids stability to the comparator circuit. Resistor 512 introduces a slight positive bias to “+” input of Op Amp 511 to ensure a well-defined state of 511 output. Depending on the type of 511 Op Amp, resistor 512 may or may not be needed. V++ at the “—” input sets the upper limit threshold for Vm that represents the maximum LED current allowed. When this limit is exceeded, 511 will change state from low to high that in turn causes transistor 508 to conduct therefore diverting the current from the LED to 508. Noted also, 508 may be of other kinds such as a MOSFET. With an added capacitor 518 for filtering and storage, the circuit shown in FIG. 5 is also suited to work with conventional triac-based AC light dimmers.
  • FIG.6 it shows yet another LED current monitoring and diversion circuit that takes off from Point “a” and Point “b” in FIG. 2.
  • the circuit has a more refined Vm reference threshold voltage derived from a band-gap precision voltage reference diode 604.
  • Reference voltage V+ obtained through the voltage divider comprising resistors 605 and 606.
  • a 1.225V Band-gap device 604 selected for ease of circuit explanation. Other band-gap voltage devices are equally applicable.
  • Vm is derived by the voltage drop across resistor 611 from the flow of the LED current.
  • Operational amplifier 609 configured as a comparator through the use of resistors 608 and 610 with V+ reference voltage applied at the “—” input terminal.
  • Op Amp 609 interfaces with the current diversion device 607 directly which in the present design a MOSFET is chosen. It is noted here that 607 may be of a different kind but would work just as effective. Noted also, no additional power supply or conditioning circuit/device is used in the present design.
  • the voltage (Point “a”) obtained from the rectifier circuit as shown in FIG. 2 is stored in capacitor 603 with diode 601 in place to prevent reverse current flow from capacitor 603 to the rectifier circuit when the instantaneous voltage at Point “a” drops below capacitor 603 voltage.
  • the forward LED voltage is kept below 30 to 33V and nearly all operational amplifiers are capable to with supply voltages from less than 5V to 38V or 40V. This fact further simplifies a practical design and reduces the component count when using the present invention.
  • the design that follows the present case in FIG. 7 will address the exceptions when the LED forward voltage drop exceeds 35V.
  • FIG. 7 the design taking off also from Point “a” and Point “b” in FIG. 2 employs a different approach to address the use of conventional triac – based AC dimmer devices with the present invention.
  • a triac –base dimmer device can generate very rich harmonic frequency contents that may produce harmful transient currents to the LED device 714 by the current –generating capacitor 103 in FIG. 2.
  • MOSFET 712 is normally on and conducting.
  • Resistor 714 measures the LED current similar to previous designs. When Vm exceeds the reference voltage plus the comparator hysteresis MOSFET will turn off, Resistor 713 will be inserted in the current path of the LED.
  • the value of 713 is such that it will limit the LED current for a period determined by the time constant in the comparator 712 composite hysteresis network.
  • 712 is an operational amplifier and configured as a voltage comparator.
  • the product of the values of resistor 711 and capacitor 707 is the time constant that determines the OFF time of MOSFET 712 and re-sampling time of Vm if the LED over current persists.
  • Resistors 708 and 711 set the steady-state hysteresis voltage.
  • Resistor 709 and zener diode act to prevent gate-source breakdown when The Op Amp 712 output voltage is excessive.
  • Capacitor 718 enhances the filter function since the insertion of resistor 713 would create added voltage transients. In practice capacitor 718 could be the same Capacitor 205 as shown in FIG. 2.
  • FIG. 8 another design addressing the LED monitoring and protection is shown.
  • This circuit is an enhanced version of the design shown in FIG. 6. It intends to broaden the application of the present invention to include the most critical environment and line conditions.
  • the enhancements are in the areas of adding intelligence and reducing stress to the circuit shown in FIG. 6.
  • the comparator circuit comprising op amp 812 and associated components now has a composite hysteresis that allows the LED current monitoring with a defined time frame each time the over-current condition is sampled. Similar to the comparator circuit in FIG. 7, the sampling time is determined by the time constant given by the product of the values of resistor 811 and capacitor 810.
  • Second enhancement is the adding of an RC (resistor – capacitor) network in the DRAIN circuit of the MOSFET device 809. Comprised by resistor 805 and capacitor 808, this network moderates the current diversion action by controlling the amplitude and time of the diverted current. It also reduces the MOSFET 809 stress by sharing the power dissipation with resistor 805. Description of the remaining circuitry in FIG. 8 is omitted here since it is identical to those in earlier Figures and descriptions were given.
  • FIG.9 and FIG.10 the figures show the potential use of the present invention in the making and production of those lights and light fixtures (i.e., accent lighting for landscape, area light for middle court lamp, bathroom lighting, chandeliers, commercial lighting and flood lights) as shown.
  • the images presented in FIG.9 and FIG.10 is by no means inclusive in the application of the present invention. There is no limit in the use of the present invention in the field of the LED lighting.
  • FIG. 11 through FIG. 15 shows the expanded use of the present invention in the inner works of LED lighting systems and auxiliary products.
  • the design shows the present invention being embodied in two separate parts.
  • the dotted line box on the left contains the design of a SWITCH ASSEMBLY while the box on the right labeled LED LIGHT ASSEMBLY holds the design of the LED driver as it was shown in FIG. 2 less the current generating capacitor front-end.
  • the concept is that the circuit in the right box resides in the LED light entity, whether it is in a bulb form or otherwise.
  • the left box is a standalone product that mates with the right box through a standard light-switch wiring circuit.
  • This design variation makes it possible to permit an LED light bulb or assembly using the present invention to replace a conventional light directly without the need to redo the wiring.
  • Both left and right boxes operate on the low-side (neutral wire) of the AC voltage input while the high-side (hot wire) remains in the light bulb socket as in the standard switch-light wiring practice.
  • FIG. 12 shows a unique LED dimming circuit that stems off the present invention. Take the LED current generating capacitor 103 in FIG.2 and break it into multiple smaller capacitor pieces (C1 through Cn) and then assemble them in a rotary or slider shorting switch form as shown by 1202 and 1201. In practice some or all of the front-end protection elements as shown in FIG.11 may be included when the assembly 1200 is made into a standalone dimmer-switch product as shown in FIG.13. Dimming action takes place when the rotary switch or the slider switch is being operated. The LED will exhibit the full brightness when all the capacitors are selected, i.e. their open ends are shorted. A totally open position in the switch is reserved for OFF function. The LED is totally turned off when this position is selected.
  • FIG. 13 shows a standalone dimmer switch that can be mounted remotely and can be connected to an LED assembly using the existed wiring. Such a device is well-suited to address the retrofit market replacing incandescent lamps with the LED lights.
  • Entities 1300 through 1302 are the standard front-end circuit elements and input quantity described in previous paragraphs.
  • the design takes a small portion of the current defined by the main capacitor 1301 and uses it to support a PWM (pulse-width modulation) dimming circuit (entities 1303 through 1308).
  • !303 is a electronic switch controlled by the output of the PWM circuit.
  • the overall design can all be placed in a light bulb using a wireless remote to control the PWM circuit, or it can be divided up whereas every element other than the LED 108 and the associated protection circuit (1311 and 1309) may be grouped as a standalone driver-dimmer device.
  • the dimming control shown in 1312 can be either a potentiometer or through the use of a wireless remote subsystem. More of the wireless embodiment will be disclosed in future drawings.
  • the circuit in FIG. 14 when put in a dimmer-switch enclosure will connect to the LED light via “+” and “-” terminals.
  • Resistor 1305 produces a pilot current (1 mA or less) to set the operation of the 3-terminal regulator.
  • the LED forward voltage drop will limit the maximum voltage applied to the regulator.
  • a typical range may be from 5 to 60 V depending on the LED power size.
  • a practical circuit showing such functionality is presented in FIG.15.
  • FIG. 15 shows a practical PWM dimmer design using the teaching described in paragraph [0062], whereas two operational amplifier circuits are used.
  • Op Amp 1505 is configured as a square-wave generator while Op Amp 1509 is wired as a voltage comparator circuit to function as the dimmer control. Being a square-wave generator, Op Amp 1505 supplies a near triangular wave signal at its negative input terminal. With this waveform and through the control by the potentiometer 1507, the output of Op Amp 1509 will exhibit a variable width pulse train that toggles MOSFET current switch 1515.
  • the Control range of P1 (1507) provides the LED dimming from fully off to fully on.
  • the PWM concept per description herein may take a product form as two separate entities, i.e., a standalone PWM dimmer switch and an LED light that is package specifically to mate with the disclosed PWM dimmer.
  • An alternative product form is to integrate the entire capacitor current generator as shown in FIG. 2 and the PWM circuit presented here all in the LED light fixture.
  • a desk-top lamp may be a typical example.
  • the function of P1 may be replaced by a remotely controllable and programmable electronic potentiometer with addressable individual identification.
  • a digital embodiment of the design is therefore also part of the invention and is elaborated in a drawing to follow.
  • a dual operational amplifier integrated circuit is a preferred choice for implementing 1505 and 1509 although discrete devices also suffice the application.
  • FIG. 16 shows a functional block diagram of a product concept that uses the teach in entities 2038 and 2039.
  • entities 1601 through 1603 are similar or identical to the circuits and elements described earlier herein.
  • the present design describes an addition of a remote control feature that replaces the potentiometer P1 in entity 1507 as shown in FIG. 15 by a wireless control scheme.
  • Element 1607 is a wireless receiver-decoder of a standard design while element 1606 is the front-end hardware. 1606 can be either an infrared receiver or a radio-frequency (RF) antenna. Entity 1607 depending on the preference of the wireless technology selected.
  • RF radio-frequency
  • Entity 1607 decodes the control information and passes it to the digital interface 1605 which in turn completes the control function in the digital PWM control circuit.
  • Entities 1608 through 1610 are standard circuit and LED elements described in FIG. 2 and elsewhere earlier.
  • the matching remote control may either be a hand-held or wall-mount device.
  • the present invention is especially efficient and cost-attractive in the deployment of LED lights in the higher frequency power source environments. Comparing with 60 or 50 Hz land-base usages, the 400 Hz aircraft AC power source requires only one-seventh or one-eighth of the capacitor size to generate the same current quantity with the same voltage value. Further, for different LED wattage applications the only change required is the value of the main current- producing capacitor. This fact makes the in-craft LED deployment task using the present invention extremely simple. The design shown in FIG. 2 is therefore equally applicable, for instance, in aircrafts for any LED light wattage; from sub one-watt to over 300 watts. Referring to FIG. 17 a simplified block diagram is shown whereas an standardized 400Hz airborne AC power source 1701 is assumed.
  • This AC source may be applied to the scheme of the present invention as shown in Figures 1 and 2. All of the subsystem designs described in the FIG. 3 through FIG. 15 are equally applicable to the higher frequency aviation applications of no exception. 1702 show details the 400 Hz AC source drives the standard capacitive current-generating system per the present invention.
  • a LED current distribution subsystem may also be included in the design. For instance when a serial connection of the LED lights for certain applications, such as the overhead multiple reading light in an airplane, is prescribed. (See FIG. 21). Said advantages of the present invention for earth-bound, land-based applications are even more augmented in the case of higher frequency aviation applications described herein.
  • FIG. 18 it shows a functional block diagram describing a unique vehicular LED lighting system employing exclusively the present invention.
  • a standard on-board battery source 1801 it drives a DC to AC power inverter 1802 of conventional design.
  • the inverter out although can be of any frequency and amplitude, it is probably desirable to set, for instance, at 400Hz and 36V for safety and ease of application.
  • the inverter output may be distributed the network 1804 through out the vehicle where the present invention (i.e., the Block 1805) is used locally to drive individual LEDs as well as grouped LEDs.
  • the inverter output may also be pre-processed using the present invention (i.e., the Block 1803) and dispatched via a distribution network 1804 to the LED lights. From the head lights, tail lights, brake and signal lights to all of the interior lights, the design concept demonstrated in FIG.18 can address all of these applications with extreme simplicity; since the current –generating capacitor is the only component needs to be changed for different wattage LEDs. Further, the system thus contemplated also will allow a single cabling system that permits the super-imposition of both the DC and AC power to be carried to reach there respective application apparatus. Simple use of capacitive and inductive elements will allow extraction and isolation of the two distinctive power usages.
  • FIG. 19 shows a functional block diagram that gives an alternative design to address the LED protection.
  • Block 1906 is a triangular wave generator. This signal is the reference to the adaptive PWM (pulse-width modulation) circuit in block 1907. When the LED current is of the correct amount the MOSFET 1905 is conducting fully. If for whatever the reason, the averaged LED current exceeds the set limit, the adaptive PWM circuit will output a pulse signal which regulates the MOSFET 1905 conduction by varying the pulse-width of the control signal applied at the MOSFET gate terminal. Resistor 1904 measures the LED current. The measured signal Vm in voltage form is processed for its average value inside Block 1907. This averaged signal is then applied adaptively inside Block 1907 to produce a PWM output.
  • This protection circuit may also be extended to include LED a dimming function. The practical circuit presented in FIG. 20 shall address this prospect.
  • FIG. 20 shows a practical circuit diagram that implements the design principle illustrated in FIG. 19 and described in preceding paragraph.
  • the design uses the standard front-end design of the present invention as shown in Block 2001.
  • the output from Block 2001 drives a on-board power supply 2002 also of the standard design found in earlier descriptions.
  • the operational amplifier circuit 2003 configured with the associated components 2004 through 2007 creates an oscillator that produces a approximated saw-tooth wave train at the negative input terminal of the Op Amp 2003. This signal is buffered through the use of a unit-gain Op Amp circuit 2017 prior to its application at the positive input terminal of the OP Amp circuit 2008.
  • the LED 2019 current measured by resistor 2018 in voltage form Vm is being process for its averaged value through a low-pass filter comprising resistor 2011 and capacitor 2012.
  • Op Amp circuit 2010 amplifies this signal and applies it to the potentiometer 2009. Resistors 2013 and 2014 determine the needed amplification.
  • the wiper of potentiometer 2009 introduces the appropriate amount of the processed Vm to the op amp configured comparator circuit 2008.
  • the output of 2008 will exhibit either a constant high level to keep MOSTET 2016 fully conducting under normal operating, or it changes to a PWM pulse-train when LED experiences over-current condition.
  • the circuit shown in FIG. 20 may also serve as a dimming control with appropriate adjustment of the circuit and control parameters. Moreover, it is also evidently that, this circuit may also serve both functions, i.e., the dimming and protection for the LED that this circuit drives.
  • FIG. 21 presents a application concept that demonstrates the versatility and flexibility when using the present invention.
  • the concept applies specifically to serially connected LED lights such as in the case of reading lights inside a commercial aircraft.
  • the design allows multiple reading lights to be connected serially sharing a constant current source on a single distribution circuit.
  • the current source is derived by means of a capacitor that has been thoroughly described in the current invention.
  • Blocks 2101 through 2104 are the standard components in the current invention and their functions have been equally described previously. Focusing on the features, the design allows individual control of each light with no interference. Further, sharing the same current, the scheme is extremely power efficient and cost-effective since all serially connected LEDs are powered by one current driver. Referring to FIG. 21, the current coming out the rectifier feeds the serially connected LEDs, LED1 through LEDn.
  • the current shorting switches S1 through Sn provides individual light ON-OFF control for all LEDs.
  • the diode array 2106) next to the switches is supplied for voltage equalization purposes. This diode array of the conventional silicon kind with forward voltage drops the are closely matched with the LEDs. This diode array is optional. Its need arises only when the number of LEDs is significant and the current source magnitude may be influenced by the switch functions of the lights.
  • S1 through Sn may also be of an electronic kind. This option further allows a central over-riding control of the switches which may be a requirement in certain applications.

Landscapes

  • Circuit Arrangement For Electric Light Sources In General (AREA)

Abstract

La présente invention concerne un nouveau système de commande et d'excitation d'éclairage à diodes électroluminescentes (DEL) à courant alternatif (CA). Le système utilise un élément réactif servant à produire le courant d'éclairage de DEL requis. Grâce aux caractéristiques inhérentes de surveillance et de protection offertes par la solution présente, le système fait preuve d'une efficacité élevée, d'un grand aspect pratique, et d'une applicabilité universelle pour toutes les applications d'éclairage à DEL basées sur le CA.
PCT/CN2010/078697 2010-11-12 2010-11-12 Système de commande de courant d'éclairage à del (diodes électroluminescentes) à réactance Ceased WO2012061999A1 (fr)

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Application Number Priority Date Filing Date Title
PCT/CN2010/078697 WO2012061999A1 (fr) 2010-11-12 2010-11-12 Système de commande de courant d'éclairage à del (diodes électroluminescentes) à réactance
CN201110364685.4A CN102404917B (zh) 2010-11-12 2011-11-04 电抗式led照明电流控制电路、驱动器及控制系统

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PCT/CN2010/078697 WO2012061999A1 (fr) 2010-11-12 2010-11-12 Système de commande de courant d'éclairage à del (diodes électroluminescentes) à réactance

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US8598796B2 (en) 2010-12-11 2013-12-03 Jae Hong Jeong Light emitting diode driver using turn-on voltage of light emitting diode
WO2013184669A1 (fr) * 2012-06-04 2013-12-12 Advanergy, Inc. Système et procédé de surveillance/commande d'appareil d'éclairage
WO2013191806A1 (fr) * 2012-06-21 2013-12-27 Altoran Chip & Systems Inc. Circuit d'attaque de diode électroluminescente
US8841862B2 (en) 2011-06-29 2014-09-23 Chong Uk Lee LED driving system and method for variable voltage input
US8901849B2 (en) 2010-12-11 2014-12-02 Jae Hong Jeong Light emitting diode driver
CN104244525A (zh) * 2014-09-12 2014-12-24 成都威邦科技有限公司 一种具有线性调光功能的led驱动系统
US8970200B2 (en) 2012-11-09 2015-03-03 Apple Inc. Systems and methods for light-load efficiency in displays
US9161398B2 (en) 2013-10-16 2015-10-13 iLight, LLC Lighting device
CN107154744A (zh) * 2017-07-20 2017-09-12 西安邮电大学 一种恒流电源电路
CN110582144A (zh) * 2019-10-14 2019-12-17 深圳市明微电子股份有限公司 自适应泄放控制电路及方法
CN110996446A (zh) * 2020-01-03 2020-04-10 中国计量大学 一种交流驱动的led器件及其在交流电电源下的发光方法
EP2775796B1 (fr) * 2013-03-05 2020-04-29 Goodrich Lighting Systems GmbH Lumière de lecture à DEL et procédé de remplacement d'une lumière de lecture à DEL
CN112067928A (zh) * 2020-09-09 2020-12-11 江苏普瑞德智能科技有限公司 一种供电系统监察装置
US20240188201A1 (en) * 2022-12-02 2024-06-06 Express Imaging Systems, Llc Field adjustable output for dimmable luminaires
CN118539269A (zh) * 2024-07-26 2024-08-23 成都光创联科技有限公司 一种激光器电流精细控制电路

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CN1688186A (zh) * 2005-03-23 2005-10-26 天津大学 220v交流led灯的驱动电路
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US9018856B2 (en) 2010-12-11 2015-04-28 Jae Hong Jeong Light emitting diode driver having phase control mechanism
US8890432B2 (en) 2010-12-11 2014-11-18 Jae Hong Jeong Light emitting diode driver
US8901849B2 (en) 2010-12-11 2014-12-02 Jae Hong Jeong Light emitting diode driver
US8598796B2 (en) 2010-12-11 2013-12-03 Jae Hong Jeong Light emitting diode driver using turn-on voltage of light emitting diode
US8928254B2 (en) 2010-12-11 2015-01-06 Altoran Chip And Systems, Inc. Light emitting diode driver
US8952620B2 (en) 2010-12-11 2015-02-10 Altoran Chip And Systems, Inc. Light emitting diode driver
US9144123B2 (en) 2010-12-11 2015-09-22 Jae Hong Jeong Light emitting diode driver having cascode structure
US8841862B2 (en) 2011-06-29 2014-09-23 Chong Uk Lee LED driving system and method for variable voltage input
WO2013184669A1 (fr) * 2012-06-04 2013-12-12 Advanergy, Inc. Système et procédé de surveillance/commande d'appareil d'éclairage
WO2013191806A1 (fr) * 2012-06-21 2013-12-27 Altoran Chip & Systems Inc. Circuit d'attaque de diode électroluminescente
US8970200B2 (en) 2012-11-09 2015-03-03 Apple Inc. Systems and methods for light-load efficiency in displays
EP2775796B1 (fr) * 2013-03-05 2020-04-29 Goodrich Lighting Systems GmbH Lumière de lecture à DEL et procédé de remplacement d'une lumière de lecture à DEL
US9161398B2 (en) 2013-10-16 2015-10-13 iLight, LLC Lighting device
CN104244525A (zh) * 2014-09-12 2014-12-24 成都威邦科技有限公司 一种具有线性调光功能的led驱动系统
CN104244525B (zh) * 2014-09-12 2016-06-08 国网山东省电力公司定陶县供电公司 一种具有线性调光功能的led驱动系统
CN107154744A (zh) * 2017-07-20 2017-09-12 西安邮电大学 一种恒流电源电路
CN110582144A (zh) * 2019-10-14 2019-12-17 深圳市明微电子股份有限公司 自适应泄放控制电路及方法
CN110996446A (zh) * 2020-01-03 2020-04-10 中国计量大学 一种交流驱动的led器件及其在交流电电源下的发光方法
CN112067928A (zh) * 2020-09-09 2020-12-11 江苏普瑞德智能科技有限公司 一种供电系统监察装置
CN112067928B (zh) * 2020-09-09 2023-02-28 江苏普瑞德智能科技有限公司 一种供电系统监察装置
US20240188201A1 (en) * 2022-12-02 2024-06-06 Express Imaging Systems, Llc Field adjustable output for dimmable luminaires
CN118539269A (zh) * 2024-07-26 2024-08-23 成都光创联科技有限公司 一种激光器电流精细控制电路

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