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WO2008029458A1 - Dispositif de transmission radio, dispositif de réception radio et système de communication sans-fil - Google Patents

Dispositif de transmission radio, dispositif de réception radio et système de communication sans-fil Download PDF

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Publication number
WO2008029458A1
WO2008029458A1 PCT/JP2006/317660 JP2006317660W WO2008029458A1 WO 2008029458 A1 WO2008029458 A1 WO 2008029458A1 JP 2006317660 W JP2006317660 W JP 2006317660W WO 2008029458 A1 WO2008029458 A1 WO 2008029458A1
Authority
WO
WIPO (PCT)
Prior art keywords
signal
pilot
wireless
pilot signal
systems
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Ceased
Application number
PCT/JP2006/317660
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English (en)
Japanese (ja)
Inventor
Katsuya Oda
Takashi Enoki
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Panasonic Corp
Panasonic Holdings Corp
Original Assignee
Panasonic Corp
Matsushita Electric Industrial Co Ltd
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Panasonic Corp, Matsushita Electric Industrial Co Ltd filed Critical Panasonic Corp
Priority to PCT/JP2006/317660 priority Critical patent/WO2008029458A1/fr
Publication of WO2008029458A1 publication Critical patent/WO2008029458A1/fr
Anticipated expiration legal-status Critical
Ceased legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/0413—MIMO systems
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/06—Receivers
    • H04B1/10—Means associated with receiver for limiting or suppressing noise or interference
    • H04B1/1027—Means associated with receiver for limiting or suppressing noise or interference assessing signal quality or detecting noise/interference for the received signal
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/08—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station
    • H04B7/0802—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station using antenna selection
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/18—Phase-modulated carrier systems, i.e. using phase-shift keying
    • H04L27/22—Demodulator circuits; Receiver circuits
    • H04L27/233—Demodulator circuits; Receiver circuits using non-coherent demodulation
    • H04L27/2332—Demodulator circuits; Receiver circuits using non-coherent demodulation using a non-coherent carrier
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2657—Carrier synchronisation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2668—Details of algorithms
    • H04L27/2673—Details of algorithms characterised by synchronisation parameters
    • H04L27/2675—Pilot or known symbols

Definitions

  • Wireless transmission device Wireless reception device, and wireless communication system
  • the present invention relates to a radio transmission apparatus, radio reception apparatus, and radio communication system having a phase noise cancellation function and a MIMO (Multiple Input Multipie Output: spatial multiplexing) communication function using multiple antennas.
  • MIMO Multiple Input Multipie Output: spatial multiplexing
  • FIG. 1 is a block diagram showing an example of a wireless receiver in a conventional wireless communication system with improved phase noise characteristics.
  • the radio receiver shown in FIG. 1 has a local “noise” canceller to improve the phase noise characteristics.
  • FIG. 2 is a characteristic diagram showing the frequency characteristics of each component of the local noise canceller in the wireless receiver of FIG.
  • the symbols in each black circle in FIG. 1 correspond to the characteristic diagrams of the respective symbols in FIG.
  • the input signal (A) input to distributor 1 of the wireless receiver shown in Fig. 1 is the modulated IF signal (BBT-OFDM) and pilot carrier (PILOT).
  • BBT-OFDM modulated IF signal
  • PILOT pilot carrier
  • ⁇ (t) is the input phase noise ⁇ (t) superimposed on f and f.
  • PLT sig PLT and f are respectively expressed by the following equations.
  • the input signal (A) is distributed by distributor 1, one is output to the pilot branch, and the other is output to the signal branch (modulation signal branch). Distribution in the pilot branch One of the signals distributed by the filter 1 is band-limited by the band-pass filter (BPF) 2 and only the component of the pilot 'carrier (PILOT) is passed through and extracted, and is further limited by the limiter amplifier 3 The At this time, the IF signal component is removed from the frequency characteristics of the output signal (B) output from BPF2 and the output signal (C) output from the limiter amplifier 3 as shown in Fig. 2 (B Therefore, only the pilot 'carrier (PILOT) component and the input phase noise 0 (t) superimposed on it are included.
  • BPF band-pass filter
  • PILOT component of the pilot 'carrier
  • the carrier frequency f has a delay time ⁇
  • local oscillator signal (D) is output from local oscillator 4.
  • the frequency characteristics of the local oscillation signal (D), in which the local oscillator 4 power is also output, are as shown in Fig. 2 (D), and the local oscillation phase (LO) signal superimposed on the local oscillation frequency (LO) signal. Noise.
  • the local oscillation signal frequency in the system is expressed as f
  • the local oscillation signal frequency f in the system is f
  • the input signal output from the distributor 1 is frequency-converted by the multiplier (mixer) 5 with the local oscillator signal (D) of four local oscillators, and the multiplier 5 Signal (E) is output.
  • the frequency characteristics of the signal (E) output from the multiplier 5 are the sum and difference components of the input signal (A) and the local oscillation signal (D) as shown in Fig. 2 (E). Exists. Therefore, the relationship between each signal component included in the signal) and the superimposed phase noise is as follows.
  • the delay compensator 7 adds a delay At to the signal) to equalize the delay time difference from the pilot branch.
  • the signal (G) of the signal branch and the pilot branch signal (C) output from the limiter amplifier 3 are frequency-converted by the frequency change 8, and the signal (H) Is output.
  • the frequency characteristic of the signal (H) output from the frequency shift 8 is the sum and difference components of the signal (G) and the signal (C) as shown in Fig. 2 (H).
  • the relationship between each signal component contained in signal (H) and the superimposed phase noise is as follows. f — (f -f) ⁇ ⁇ (t- ⁇ )- ⁇ 0 (t- T - ⁇ ) - ⁇ ( ⁇ ⁇ ⁇ -At) ⁇
  • the delay time of the delay corrector 7 is
  • the delay ⁇ t is added to equalize the delay time difference between the signal branch and the pilot branch, so the above equation can be rearranged as follows.
  • the frequency of the output signal component is the frequency of the local oscillation signal (f) in the system related to the frequency of the input signal.
  • phase noise ⁇ that is, constant.
  • the sideband of the signal is inverted at the input and output.
  • the phase noise of the output signal is canceled by the input phase noise ⁇ (X) and becomes the phase noise ⁇ (X) of the local oscillation signal in the system instead. That is, the phase noise ⁇ of the local oscillation signal in the system
  • the signal (H) frequency-converted by the frequency conversion 8 is band-limited so that only the difference component and only the signal component pass through the band-pass filter (BPF) 9, and the signal is transmitted from the BPF 9.
  • (I) is output.
  • the frequency characteristics of this signal (I) are such that only the signal component of the difference component exists by removing the pilot / carrier component in the sum and difference components of signal (H). .
  • the relationship between the signal component included in the signal (I) and the superimposed phase noise is expressed by the following equation.
  • phase noise of the output signal is canceled by the phase noise ⁇ (X) superimposed on the input signal, and instead becomes only the phase noise ⁇ (X) of the local oscillation signal in the system. If the phase noise ⁇ (X) of the local oscillation signal is sufficiently small, the phase noise of the input signal is sufficiently reduced and output.
  • Patent Document 1 JP 2002-152158 A
  • FIG. 3 is a block diagram showing a configuration of a radio transmission apparatus and a radio reception apparatus when a phase noise cancellation technique is applied during MIMO communication in a conventional radio communication system.
  • the wireless communication system shown in FIG. 3 includes a wireless transmission device 10 and a wireless reception device 20 that perform MIMO communication.
  • the baseband signal output from the transmission baseband unit (transmission BB unit) 11 of the wireless transmission device 10 is separated into two systems by the MIMO separation unit 12.
  • One baseband signal is orthogonally modulated by the orthogonal modulation unit 13a, and further input to the transmission RF unit 14a and frequency-converted to an RF signal (radio signal) by the local oscillator 15.
  • the other baseband signal is quadrature modulated by the quadrature modulation unit 13b, further input to the transmission RF unit 14b, and frequency-converted to an RF signal (radio signal) by the local oscillator 15.
  • a radio signal is transmitted from the transmission antenna 16a of the transmission RF unit 14a via the path 1 and the path 2, and the radio signal is transmitted from the transmission antenna 16b of the transmission RF unit 14b via the path 3 and the path 4. Issue is sent.
  • the pilot signal for canceling the phase noise is transmitted through all propagation paths. It is superimposed on the line signal.
  • the radio signal transmitted from the transmission antenna 16a via the path 1 has propagation path phase information ⁇
  • propagation path phase information ⁇ 1 is added, and propagation path phase information ⁇ 2 is added to the radio signal transmitted from the transmission antenna 16a via the path 2. Further, the propagation path phase information ⁇ 3 is added to the radio signal transmitted from the transmission antenna 16b via the path 3, and the propagation path phase information ⁇ 4 is transmitted to the radio signal transmitted from the transmission antenna 16b via the path 4. Is added.
  • receiving antenna 21a receives a radio signal to which propagation path phase information ⁇ 1 is added from path 1, and a radio signal to which propagation path phase information ⁇ 3 is added from path 3. Receive. That is, the receiving antenna 21a receives the radio signals of the route 1 and the route 3 mixed.
  • the receiving antenna 21b receives a radio signal to which the propagation path phase information ⁇ 2 is added from the path 2 and receives a radio signal to which the propagation path phase information ⁇ 4 is added from the path 4.
  • the receiving antenna 2 lb receives in a state where the wireless signals of the route 2 and the route 4 are mixed.
  • a radio signal (including propagation path phase information ⁇ 1 and ⁇ 3) received by the receiving antenna 21a is amplified by the amplifier 22a and then mixed with the reference signal of the local oscillator 24 by the multiplier 23a.
  • the frequency is converted into an IF signal, and further input to the distributor 27a via the band pass filter 25a and the variable amplifier 26a.
  • This IF signal is distributed to the modulated signal branch and the pilot branch by the distributor 27a, and is input to the orthogonal demodulator 29a via the delay corrector 28a in the modulated signal branch.
  • the pilot signal is extracted by the band pass filter 30a, amplified by the amplifier 31a, and then input to the quadrature demodulator 29a.
  • the quadrature demodulator 29a cancels the phase noise by subtracting (E ⁇ F) the signal (F) that is the pilot signal from the signal (E) that is the IF signal. At this time, the propagation path phase information ⁇ 1 of the signal of the path 1 is also canceled out. Similarly, the propagation path phase information ⁇ 3 of the signal of the path 3 is also canceled.
  • Radio signals (including propagation path phase information 0 2 and 0 4) received by the reception antenna 21b of the radio reception device 20 are amplified by the amplifier 22b, and then are local oscillators in the multiplier 23b. It is mixed with 24 reference signals and converted to an IF signal. It is input to the distributor 27b via the filter 25b and the variable amplifier 26b. This IF signal is distributed to the modulated signal branch and the pilot branch by the distributor 27b, and is input to the quadrature demodulator 29b via the delay corrector 28b in the modulated signal branch. In the pilot branch, the pilot signal is extracted by the band pass filter 30b, amplified by the amplifier 31b, and then input to the quadrature demodulator 29b.
  • the quadrature demodulator 29b cancels the phase noise by subtracting (E ⁇ F) the signal (F) that is the pilot signal from the signal (E) that is the IF signal. At this time, the propagation path phase information ⁇ 2 of the signal of path 2 is also canceled. Similarly, the propagation path phase information ⁇ 4 of the signal of the path 4 is also canceled.
  • the MIMO synthesizer 32 performs the MIMO matrix operation. As a result, it becomes impossible to separate multiple data sequences, and it becomes impossible to output a signal to the reception baseband unit (reception BB unit) 33.
  • An object of the present invention is to provide a wireless transmission device, a wireless reception device, and a wireless communication system capable of realizing both a phase noise cancellation function and a MIMO communication function. Means for solving the problem
  • a wireless reception device of the present invention is a wireless reception device of a wireless communication system that performs n systems (n is a plurality) of MIMO communications, and in a wireless transmission device of a communication partner, among the n systems of MIMO paths
  • a pilot means is superimposed on an arbitrary m system (m is a natural number, n> m), receiving means for receiving signals transmitted by multiple systems, received signal power, extracting means for extracting the pilot signals, and all And a plurality of orthogonal demodulation means for performing orthogonal demodulation on the received signal transmitted through the MIMO path using the extracted pilot signal.
  • a radio transmission apparatus includes a separating unit that separates a transmission signal into n MIMO paths, a pilot signal generating unit that generates a pilot signal, and the pilot signal superimposed on m of the n systems.
  • the wireless communication system of the present invention is a wireless transmission device using n systems (n is a plurality) of MIMO communications.
  • a wireless communication system for transmitting a signal to a wireless reception device wherein the wireless transmission device includes a separation unit that separates a transmission signal into n MIMO paths, a pilot signal generation unit that generates a pilot signal, A superimposing unit that superimposes a pilot signal on m systems (m is a natural number, n> m) of the n systems, and a transmitting unit that transmits signals to the wireless receiving apparatus in n systems.
  • An apparatus includes: a receiving unit that receives a signal transmitted from a wireless transmission device of a communication partner; an extracting unit that extracts the pilot signal from the received signal; and the extraction for the received signal transmitted through all MIMO paths. And a plurality of orthogonal demodulation means for performing orthogonal demodulation using the pilot signal thus obtained.
  • the wireless transmission device superimposes the pilot signal for phase noise cancellation on only one of the propagation paths of a plurality of systems, and the wireless reception device extracts
  • the signal for quadrature demodulation of the signals of all propagation paths the phase information of the propagation path is not lost during quadrature demodulation, so the phase noise cancellation function and the MIMO communication function can be realized together. Good communication characteristics can be obtained.
  • FIG. 1 is a block diagram showing an example of a wireless receiving device in a conventional wireless communication system
  • FIG. 2 is a characteristic diagram showing frequency characteristics of each component of the local noise canceller in the wireless receiver of FIG.
  • FIG. 3 is a block diagram showing a configuration of a wireless transmission device and a wireless reception device when phase noise cancellation technology is applied during MIMO communication in a conventional wireless communication system.
  • FIG. 4 is a block diagram showing configurations of a wireless transmission device and a wireless reception device of the wireless communication system according to Embodiment 1 of the present invention.
  • FIG. 5 is a block diagram showing configurations of a wireless transmission device and a wireless reception device of the wireless communication system according to Embodiment 2 of the present invention.
  • FIG. 6 is a block diagram showing configurations of a wireless transmission device and a wireless reception device of the wireless communication system according to the third embodiment of the present invention.
  • FIG. 4 is a block diagram showing configurations of radio transmitting apparatus 100 and radio receiving apparatus 200 of the radio communication system according to Embodiment 1 of the present invention.
  • the wireless communication system shown in Fig. 4 shows a case where communication is performed by two systems of MIMO for easy understanding.
  • Radio transmission apparatus 100 includes transmission baseband unit (transmission BB unit) 101, MIMO separation unit 102, orthogonal modulation units 103a and 103b, pilot signal generation unit 104, adder 105a, local oscillator 106, transmission RF unit 107a and 107b and transmission antennas 108a and 108b are provided.
  • radio receiving apparatus 200 includes receiving antennas 201a and 201b, amplifiers 202a and 202b, local oscillator 203, multipliers 204a and 204b, bandpass filters 205a and 205b, variable amplifiers 206a and 206b, and a first distribution. 207, delay correctors 208a and 208b, quadrature demodulation units 209a and 209b, band pass filter 210, amplifier 211, second distributor 212, MIMO synthesis unit 213, and reception baseband unit (reception BB unit) 214.
  • transmission BB section 101 In radio transmission apparatus 100, transmission BB section 101 generates a baseband signal and outputs it to Ml MO separation section 102. MIMO separation section 102 separates the baseband signal into two systems. Quadrature modulation sections 103a and 103b perform quadrature modulation on each baseband signal separated into two systems.
  • Pilot signal generation section 104 generates a pilot signal for phase noise cancellation.
  • Adder 105a mixes the pilot signal with the modulation signal output from quadrature modulation section 103a.
  • the local oscillator 106 generates a local oscillation signal (local signal) and outputs it to the transmission RF units 107a and 107b.
  • the transmission RF units 107a and 107b frequency-convert the modulation signal into a radio signal (RF signal) using the input local oscillation signal.
  • the transmitting antennas 108a and 108b transmit radio signals to the wireless receiving device 200.
  • the radio signal transmitted from the transmitting antenna 108a is transmitted through the path 1 to the propagation path phase information.
  • the receiving antenna 201a of the wireless receiving device 200 When it is received by the receiving antenna 201a of the wireless receiving device 200 with ⁇ 1 added.
  • the signal is received by the receiving antenna 201b of the radio receiving apparatus 200 through the path 2 with the propagation path phase information ⁇ 2 added thereto.
  • the radio signal transmitted from the transmission antenna 108b is received by the reception antenna 201a of the radio reception device 200 via the path 3 with the propagation path phase information ⁇ 3 added, and via the path 4.
  • the signal is received by the receiving antenna 201b of the radio receiving apparatus 200 with the propagation path phase information ⁇ 4 added.
  • receiving antenna 201 a receives a radio signal to which propagation path phase information ⁇ 1 has been added via path 1, and propagates path phase information via path 3.
  • a radio signal with ⁇ 3 added is received.
  • the receiving antenna 201b receives a radio signal to which the propagation path phase information ⁇ 2 is added via the path 2, and receives a radio signal to which the propagation path phase information ⁇ 4 is added via the path 4. To do.
  • the amplifiers 202a and 202b amplify the radio signals received by the respective receiving antennas 201a and 201b.
  • the local oscillator 203 generates a local oscillation signal (local signal) and outputs it to the multipliers 204a and 204b.
  • Multipliers 204a and 204b frequency-convert radio signals (RF signals) received from the respective amplifiers 202a and 202b into IF signals using the local transmission signals from local transmitter 203.
  • the band pass filters 205a and 205b extract only signals in a desired frequency band with the signal power frequency-converted by the multipliers 204a and 204b, respectively.
  • the variable amplifiers 206a and 206b variably amplify signals in desired frequency bands output from the band pass filters 205a and 205b, respectively.
  • the first distributor 207 distributes the signal output from the variable amplifier 206a in two directions, ie, a modulated signal branch and a pilot branch.
  • the band pass filter 210 extracts a pilot signal from the signal distributed to the pilot branch by the first distributor 207 and outputs it to the amplifier 211.
  • the amplifier 211 amplifies the pilot signal extracted by the band pass filter 210 and outputs it to the second distributor 212.
  • the second distributor 212 distributes the pilot signal output from the amplifier 211 to two systems and outputs it to the quadrature demodulator 209a and the quadrature demodulator 209b.
  • Delay corrector 208a delays the modulated signal of the modulated signal branch distributed by first distributor 207, and outputs the delayed signal to quadrature demodulator 209a.
  • Quadrature demodulator 209a uses the second distribution
  • the pilot signal output from the unit 212 and the output signal from the delay corrector 208a are frequency-multiplied and subjected to quadrature demodulation. That is, the quadrature demodulator 209a converts the pilot signal corresponding to the propagation path phase information ⁇ 1 into the signal to which the propagation path phase information ⁇ 1 of the path 1 is added and the signal to which the propagation path phase information ⁇ 3 of the path 3 is added.
  • Quadrature demodulation is performed by multiplying each frequency.
  • Delay corrector 208b gives a delay to the modulated signal output from variable amplifier 206b and outputs the delayed signal to quadrature demodulator 209b.
  • the orthogonal demodulator 209b multiplies the pilot signal distributed by the second distributor 212 and the output signal from the delay corrector 208b by frequency, and performs orthogonal demodulation. That is, the orthogonal demodulation unit 209b adds the pilot signal corresponding to the propagation path phase information ⁇ 1 to the signal to which the propagation path phase information ⁇ 2 of path 2 is added and the propagation path phase information ⁇ 4 of path 4 Each signal is orthogonally demodulated by frequency multiplication.
  • the phase noise of the local oscillator is canceled in the signal of each propagation path after quadrature demodulation.
  • MIMO combining section 213 uses the path 1 signal and path 3 signal output from quadrature demodulation section 209a, and the path 2 signal and path 4 signal output from quadrature demodulation section 209b to form a matrix. The calculation is performed, and the two baseband signals obtained are serialized (MIMO synthesis) and output to the reception baseband unit 214.
  • the reception baseband unit (reception BB unit) 21 4 converts the baseband signal output from the MIMO synthesis unit 213 and outputs the converted signal to a circuit in a subsequent process.
  • the baseband signal output from the transmission BB unit 101 of the wireless transmission device 100 is separated into two systems by the MIMO separation unit 102. Further, the separated baseband signals are orthogonally modulated by the orthogonal modulators 103a and 103b, respectively.
  • the phase noise canceling pilot signal generated by pilot signal generating section 104 is superimposed on the modulated signal output from quadrature modulator 103a.
  • transmission RF section 107a the modulated signal on which the pilot signal is superimposed is converted into a radio signal (RF signal) and transmitted from transmission antenna 108a.
  • the modulated signal output from the quadrature modulator 103b is converted into a radio signal (RF signal) and transmitted from the transmission antenna 108b.
  • the radio signal transmitted from the transmission antenna 108a of the radio transmission apparatus 100 is received by the reception antenna 201a of the radio reception apparatus 200 with the propagation path phase information ⁇ 1 added via the path 1.
  • the propagation path phase information ⁇ 2 is added via the path 2 and received by the reception antenna 201b of the radio reception apparatus 200.
  • the radio signal transmitted from the transmission antenna 108b of the wireless transmission device 100 is received by the reception antenna 201a of the wireless reception device 200 through the path 3 with the propagation path phase information ⁇ 3 added thereto, and is transmitted through the path 4.
  • the propagation path phase information ⁇ 4 is added and received by the reception antenna 201b of the radio reception apparatus 200.
  • the radio signal of path 1 (propagation phase information ⁇ 1) and the radio signal of path 3 (propagation phase information ⁇ 3) received by the receiving antenna 201a are amplified by the amplifier 202a and then locally oscillated.
  • the frequency is converted by the multiplier 204a using the local oscillation signal of the unit 203, only the component of the desired frequency band is extracted by the band pass filter 205a, and is variably amplified by the variable amplifier 206a.
  • the radio signal of the path 2 (propagation phase information ⁇ 2) and the radio signal of the path 4 (propagation phase information ⁇ 4) received by the receiving antenna 201b are amplified by the amplifier 202b and then the local oscillator 203
  • the frequency is converted by the multiplier 204b using the local oscillation signal, only the component of the desired frequency band is extracted by the band pass filter 205b, and variably amplified by the variable amplifier 206b.
  • the signal output from the variable amplifier 206a is distributed in two directions of the modulated signal branch and the pilot branch.
  • the pilot signal including the propagation path phase information ⁇ 1 of the path 1 is extracted from the signal power distributed to the pilot branch.
  • the pilot signal is amplified by the amplifier 211, distributed to two systems by the second distributor 212, and input to the quadrature demodulator 209a and the quadrature demodulator 209b.
  • the signal distributed to the modulation signal branch is delayed by the delay corrector 208a, Input to the demodulator 209a.
  • the signal output from the variable amplifier 206b is delayed by the delay corrector 208b and input to the quadrature demodulator 209b.
  • the quadrature demodulator 209a uses the pilot signal corresponding to the propagation path phase information ⁇ 1, and uses the pilot signal corresponding to the propagation path phase information ⁇ 1 and the wireless signal of the path 3 (propagation phase information ⁇ 1) Quadrature demodulation is performed for 3). Further, the quadrature demodulator 209b uses the pilot signal corresponding to the propagation path phase information ⁇ 1 and uses the pilot signal corresponding to the propagation path phase information ⁇ 1 and the wireless signal of the path 4 (propagation phase information ⁇ 2) and the wireless signal of the path 4 (propagation phase information ⁇ 4 ) Is subjected to quadrature demodulation.
  • the synthesizing unit 213 performs matrix calculation using these signals.
  • the two baseband signals obtained by the matrix operation are serialized by the synthesizer 213 and converted by the receiver 213.
  • radio reception apparatus 200 all received radio signals (propagation paths) using the pilot signal containing the propagation path phase information of one propagation path are used.
  • quadrature demodulation of the phase information ⁇ 1, ⁇ 2, ⁇ 3, ⁇ 4
  • the phase noise of the local oscillator can be canceled and the relative relationship of the transmission path phase information of each propagation path is changed. Because there is no ⁇ matrix operation can be performed.
  • pilot signals are extracted from a plurality of reception systems, and signals of all paths are orthogonally demodulated using the extracted pilot signals having the highest signal level.
  • FIG. 5 is a block diagram showing configurations of radio transmitting apparatus 100 and radio receiving apparatus 200a of the radio communication system according to Embodiment 2 of the present invention.
  • a radio reception apparatus 200a shown in FIG. 5 is provided with a first distributor 207a, a bandpass filter 210a and an amplifier 21la in one reception system, and a first distributor 207b, a bandpass filter 210b and an amplifier in the other reception system. Provide a width 21 lb.
  • the wireless reception device 200a includes the wireless reception device 200 shown in FIG. In contrast, a configuration in which a comparator 215 is added is adopted.
  • the first distributor 207a distributes the signal output from the variable amplifier 206a in two directions, ie, a modulated signal branch and a pilot branch.
  • the band pass filter 210a extracts the pilot signal from the signal distributed to the pilot branch by the first distributor 207a and outputs it to the amplifier 21 la.
  • the amplifier 21 la amplifies the pilot signal extracted by the band pass filter 210 a and outputs it to the comparator 215.
  • the first distributor 207b distributes the signal output from the variable amplifier 206b in two directions of a modulated signal branch and a pilot branch.
  • the band pass filter 210b extracts a pilot signal from the signal distributed to the pilot branch by the first distributor 207b and outputs it to the amplifier 21 lb.
  • the amplifier 21 lb amplifies the pilot signal extracted by the band pass filter 210b and outputs the amplified signal to the comparator 215.
  • Comparator 215 compares the signal level of the pilot signal output from amplifier 21 la with the signal level of the pilot signal output from amplifier 21 1 lb, and determines the pilot signal having the higher signal level as the first signal. 2 Outputs to the distributor 212. As a result, the pilot signal having the better quality is supplied to the orthogonal demodulation unit 209a and the orthogonal demodulation unit 209b.
  • a transmission path on which a pilot signal is superimposed is determined based on downlink propagation path information such as a subcarrier signal level of frequencies around the pilot signal.
  • FIG. 6 is a block diagram showing configurations of radio transmitting apparatus 100a and radio receiving apparatus 200a of the radio communication system according to Embodiment 3 of the present invention.
  • the radio transmission device 100a shown in FIG. 6 is provided with adders 105a and 105b in each transmission system. 6 employs a configuration in which a determination unit 109 and a switch 110 are added to the wireless transmission device 100 illustrated in FIG. 4 and FIG.
  • the radio receiving device 200a may have the same configuration as the radio receiving device 200 shown in FIG.
  • the determination unit 109 constantly monitors the spatial propagation state of the downlink propagation path and monitors the subcarrier signal level. The information indicating the determination result is output to the switch 110. Based on the determination result of the determination unit 109, the switch 110 outputs the pilot signal generated by the pilot signal generation unit 104 to either the adder 105a or the adder 105b.
  • the phase noise cancellation function and the MIMO communication function are optimally switched by switching the propagation path on which the pilot signal is superimposed to the optimal path according to the spatial propagation state. It can be realized together.
  • the power of the present invention described for two systems of MIMO communication is not limited to this, and can also be applied to three or more systems of MIMO communication.
  • the case where the pilot signal is superimposed on one system has been described.
  • the present invention is not limited to this.
  • the pilot signal is superimposed on two systems.
  • n systems n is a multiple number
  • m is a natural number, n> m.
  • the present invention can also be applied to an apparatus having a direct conversion configuration, and can also be applied to an apparatus having a Low-IF configuration.
  • the present invention II can also be applied to multicarrier communication such as OFDM (Orthogonal Frequency Division Multiplexing).
  • OFDM Orthogonal Frequency Division Multiplexing
  • the present invention can improve the phase noise characteristics while performing MIMO communication, it is suitable for use in various wireless communication devices such as mobile phones, PHS, wireless LANs, etc. It is.

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  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Noise Elimination (AREA)

Abstract

L'invention concerne un système de communication radio capable d'offrir une fonction de suppression de bruit de phase et une fonction de communication MIMO (entrées multiples, sorties multiples). S'il existe une pluralité de voies de propagation dans Le système de communication sans-fil, un dispositif de transmission radio (100) superpose un signal pilote de suppression de bruit de phase à une seule voie de propagation. Un dispositif de transmission radio (200) extrait et emploie le signal pilote pour des démodulations de quadrature des signaux de toutes les voies de propagation. C'est à dire que dans le dispositif de transmission radio (200), le signal pilote est extrait par un filtre passe-bande (210), amplifié par un amplificateur (211), distribué dans deux systèmes par un deuxième distributeur (212), puis employé par des éléments de démodulation de quadrature (209a, 209b) afin de réaliser les démodulation de quadrature des signaux de toutes les voies de propagation.
PCT/JP2006/317660 2006-09-06 2006-09-06 Dispositif de transmission radio, dispositif de réception radio et système de communication sans-fil Ceased WO2008029458A1 (fr)

Priority Applications (1)

Application Number Priority Date Filing Date Title
PCT/JP2006/317660 WO2008029458A1 (fr) 2006-09-06 2006-09-06 Dispositif de transmission radio, dispositif de réception radio et système de communication sans-fil

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
PCT/JP2006/317660 WO2008029458A1 (fr) 2006-09-06 2006-09-06 Dispositif de transmission radio, dispositif de réception radio et système de communication sans-fil

Publications (1)

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WO2008029458A1 true WO2008029458A1 (fr) 2008-03-13

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Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2002152158A (ja) * 2000-11-15 2002-05-24 Hitachi Kokusai Electric Inc 地上デジタルｔｖ放送伝送方法及び地上デジタルｔｖ放送システム
JP2004048093A (ja) * 2002-07-08 2004-02-12 Hitachi Kokusai Electric Inc 無線通信装置
JP2004072458A (ja) * 2002-08-07 2004-03-04 Nippon Telegr & Teleph Corp <Ntt> 搬送波周波数誤差推定回路、無線信号受信装置
JP2004080110A (ja) * 2002-08-09 2004-03-11 Samsung Yokohama Research Institute Co Ltd 直交周波数分割多重通信システム、及び直交周波数分割多重無線機
JP2006101245A (ja) * 2004-09-30 2006-04-13 Toshiba Corp 受信装置

Patent Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2002152158A (ja) * 2000-11-15 2002-05-24 Hitachi Kokusai Electric Inc 地上デジタルｔｖ放送伝送方法及び地上デジタルｔｖ放送システム
JP2004048093A (ja) * 2002-07-08 2004-02-12 Hitachi Kokusai Electric Inc 無線通信装置
JP2004072458A (ja) * 2002-08-07 2004-03-04 Nippon Telegr & Teleph Corp <Ntt> 搬送波周波数誤差推定回路、無線信号受信装置
JP2004080110A (ja) * 2002-08-09 2004-03-11 Samsung Yokohama Research Institute Co Ltd 直交周波数分割多重通信システム、及び直交周波数分割多重無線機
JP2006101245A (ja) * 2004-09-30 2006-04-13 Toshiba Corp 受信装置

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