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WO2008044268A1 - Appareil et procédé de transmission - Google Patents

Appareil et procédé de transmission Download PDF

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Publication number
WO2008044268A1
WO2008044268A1 PCT/JP2006/319992 JP2006319992W WO2008044268A1 WO 2008044268 A1 WO2008044268 A1 WO 2008044268A1 JP 2006319992 W JP2006319992 W JP 2006319992W WO 2008044268 A1 WO2008044268 A1 WO 2008044268A1
Authority
WO
WIPO (PCT)
Prior art keywords
phase
signal
constant envelope
envelope signals
control signal
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Ceased
Application number
PCT/JP2006/319992
Other languages
English (en)
Japanese (ja)
Inventor
Kazuhiko Ikeda
Takashi Izumi
Takashi Enoki
Shoichi Fujita
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Panasonic Corp
Panasonic Holdings Corp
Original Assignee
Panasonic Corp
Matsushita Electric Industrial Co Ltd
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Panasonic Corp, Matsushita Electric Industrial Co Ltd filed Critical Panasonic Corp
Priority to PCT/JP2006/319992 priority Critical patent/WO2008044268A1/fr
Publication of WO2008044268A1 publication Critical patent/WO2008044268A1/fr
Anticipated expiration legal-status Critical
Ceased legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/02—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation
    • H03F1/0205—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers
    • H03F1/0294—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers using vector summing of two or more constant amplitude phase-modulated signals

Definitions

  • the present invention relates to a transmission apparatus and a transmission method, and in particular, LINC (Linear Amplification with
  • the present invention relates to a transmission apparatus and a transmission method for amplifying a transmission signal using a nonlinear components method.
  • LINC Linear Amplification with Nonlinear Components
  • FIG. 1 is a block diagram showing a configuration of a conventional LINC transmission circuit.
  • the constant envelope signal generator 11 generates two constant envelope signals S l (t) and S2 (t) from the input signal S (.
  • These constant envelope signals Sl (t), S2 (t) is explained by equations:
  • the input signal S (t) is expressed by the following equation (1), two constant envelope signals S l (t), S2 (t (2) and (3), the constant envelope signals S 1 (t) and S2 (t) are constant envelope signals with a constant amplitude direction.
  • FIG. 2 is a diagram showing signals of the transmission circuit 10 according to the conventional LINC method shown in FIG. 1 as a vector of orthogonal plane coordinates. That is, FIG. 2 is a diagram for explaining the operation of the constant envelope signal generation unit 11 of FIG. 1, and the signal vectors are displayed on the orthogonal plane change coordinates.
  • the input signal S (t) is represented by the sum of the two constant envelope signals Sl (t) and S2 (t) whose amplitude is VmaxZ2.
  • the two constant envelope signals Sl (t) and S2 (t) are amplified by the amplifier 12-1 and the amplifier 12-2, respectively.
  • the gains of the amplifier 12-1 and the amplifier 12-2 are G
  • the output signals of the amplifier 12-1 and the amplifier 12-2 are GXSl (t) and GXS2 (t), respectively.
  • GXS (t) When these signals are vector-synthesized by the synthesizer 13, an output signal GXS (t) can be obtained.
  • each of the amplifier 12-1 and the amplifier 12-2 amplifies a constant envelope signal having a constant amplitude. Therefore, since it is possible to amplify in the nonlinear region of the amplifier 12-1 and the amplifier 12-2, that is, the saturation region, the power efficiency of the amplifier 12-1 and the amplifier 12-2 can be increased.
  • the LINC transmission circuit 10 shown in FIG. 1 includes amplifiers 12-1, 12-2, which are ideal class B amplifiers, and a synthesizer 13, which is an isolation synthesizer.
  • PAPR the ratio of the average power to the maximum power of the transmitted signal
  • Z maximum power the ratio of the average power to the maximum power of the transmitted signal
  • Figure 3A the relationship between the average power Z maximum power and the efficiency of transmitter circuit 10 is shown in Figure 3A. As shown. As shown in FIG. 3A, as the average power Z maximum power decreases, that is, as PAPR increases, the efficiency of the transmission circuit 10 linearly deteriorates.
  • Patent Document 1 In order to suppress a decrease in efficiency of the transmission circuit 10 due to an increase in PAPR, Patent Document 1 describes that LI A lossless synthesizer or switching amplifier is used as the synthesizer 13 of the NC transmission circuit 10. By using a lossless synthesizer or a switching amplifier, no reactive power is generated in the load resistance, so that the efficiency of the transmission circuit 10 can be further improved.
  • the decrease in the efficiency of the transmission circuit 10 is not in a linear relationship with the increase in PAPR. Because the degradation method is not linear, efficiency degradation can be reduced for signals with large PAPR.
  • Patent Document 1 Japanese Translation of Special Publication 2002-510927
  • An object of the present invention is to provide a transmission device and a transmission method capable of reducing signal distortion while keeping the circuit scale small.
  • the transmission apparatus includes a constant envelope signal generation unit that generates first and second constant envelope signals from an input signal, and the generated first and second generated envelopes.
  • First and second amplifying means for respectively amplifying the above-described constant envelope signal, combining means for combining the first and second constant envelope signals after amplification to obtain a combined signal, and the combining And a variable phase means for controlling the phase of the signal.
  • the two constant envelope signals are generated from the input signal, the two constant envelope signals are amplified, and the two constant envelope signals after the amplification are combined to form the LINC method. Because it is possible to acquire a synthesized signal that is an amplified signal for the input signal and control the phase of the resulting synthesized signal, the signal distortion can be reduced by adjusting the output load phase of the synthesized signal. Can do.
  • FIG. 1 is a block diagram showing a main configuration of a conventional LINC transmission device.
  • FIG.2 Diagram for explaining the operation of a conventional LINC transmitter
  • FIG. 4 is a block diagram showing a main configuration of the transmitting apparatus according to Embodiment 1 of the present invention.
  • FIG. 6 is a block diagram showing a main configuration of a transmitting apparatus according to Embodiment 2 of the present invention.
  • FIG. 8 is a block diagram showing a main configuration of a transmitting apparatus according to Embodiment 3 of the present invention.
  • FIG. 9 is a block diagram showing a main configuration of a transmitting apparatus according to Embodiment 4 of the present invention.
  • FIG. 10 is a circuit diagram showing the main configuration of the synthesis unit according to the above embodiment.
  • FIG. 11 is a circuit diagram showing a main configuration of a circuit equivalent to the synthesis unit according to the embodiment.
  • FIG. 12 is a circuit diagram showing a main configuration of the synthesis unit according to the embodiment.
  • FIG. 4 shows the main configuration of the transmitting apparatus according to Embodiment 1 of the present invention.
  • the transmitter 100 shown in Fig. 4 includes a constant envelope signal generator 110, amplifiers 120-1, 120-2, and lossless synthesis.
  • Device 130, variable phase device 140, and control unit 150 are constant envelope signal generator 110 and control unit 150.
  • the constant envelope signal generator 110 generates two constant envelope signals SI (t), S2 from the input signal S (
  • Amplifiers 120-1 and 120-2 amplify the constant envelope signals Sl (t) and S2 (t), respectively, and eliminate the amplified constant envelope signals GXSl (t) and GXS2 (t). Output to loss synthesizer 130.
  • G represents the gain of the amplifiers 120-1 and 120-2.
  • the lossless synthesizer 130 synthesizes the constant envelope signals GXS l (t) and GXS2 (t) amplified by the amplifiers 120-1 and 120-2, and the resulting synthesized signal GXS (t) Output to variable phase shifter 140.
  • the lossless synthesizer 130 also includes a force such as a Chireix synthesizer or a balun.
  • variable phase shifter 140 controls the phase of the combined signal G X S (t) based on the phase control signal output from the phase control signal generation unit 152.
  • the control unit 150 includes an ACLR detection unit 151 and a phase control signal generation unit 152.
  • the ACLR detection unit 151 measures ACLR using the combined signal GXS (t), and the measurement result is a phase control signal generation unit. Output to 152.
  • the phase control signal generation unit 152 is connected to the ACLR detection unit 151.
  • a phase control signal is generated based on the ACLR measurement result, and the generated phase control signal is output to the variable phase shifter 140.
  • the relationship between the ACLR measurement result and the phase control signal will be described later.
  • the constant envelope signal generator 110 generates two constant envelope signals SI (t) and S2 (t) from the input signal S (t), and the two constant envelope signals Sl (t) and S2 (t) is amplified by amplifiers 120-1 and 120-2, respectively.
  • the amplified constant envelope signals GX Sl (t) and GXS2 (t) are combined by the lossless combiner 130, and the resultant combined signal GX S (t) is output to the variable phase shifter 140.
  • the phase of the synthesized signal G X S (t) is controlled by the variable phase shifter 140 based on the phase control signal output from the phase control signal generation unit 152.
  • the phase control signal is a measurement result of ACLR measured by ACLR detector 151.
  • the result is generated by reference.
  • the phase control signal will be described with reference to FIG. Figure 5 shows the correspondence between the ACLR measurement results and the output load phase of the lossless synthesizer 130.
  • the horizontal axis shows the load phase ([degrees]) and the right vertical axis shows the ACLR ([dB]). Yes.
  • the phase control signal for controlling the variable phase shifter 140 so as to minimize the ACLR measurement result and adjusting the output load phase is the phase control signal generator 152.
  • the phase of the variable phase shifter 140 is controlled so as to reduce the ACLR, and as a result, the signal distortion can be reduced.
  • the two constant envelope signals Sl (t) and S2 (t) are amplified by the amplifiers 120-1 and 120-2, and the amplified GX Sl is amplified.
  • GX S2 (t) is synthesized by the lossless synthesizer 130, and the variable phase shifter 140 is controlled by the phase control signal output from the phase control signal generator 152, and the synthesized signal GXS
  • the output load phase of (t) was controlled.
  • the output load phase of the composite signal GXS (t) is controlled so that the ACLR of the composite signal GXS (t) detected by the ACLR detection unit 151 becomes small. Therefore, it is possible to reduce signal distortion caused by a large signal component leaking out of the signal band, and it is possible to prevent an increase in circuit size.
  • FIG. 6 shows the main configuration of the transmission apparatus according to the present embodiment.
  • the same components as those in FIG. 4 are denoted by the same reference numerals as those in FIG. 6 includes a current detection unit 153, a level detection unit 154, a power efficiency calculation unit 155, and a phase control signal generation unit 156 instead of the ACLR detection unit 151 and the phase control signal generation unit 152. And then.
  • the current detection unit 153 detects the current flowing through the amplifier 120-1 or 120-2 and outputs the obtained current value to the power efficiency calculation unit 155.
  • the level detector 154 is a combination of The level of (t) is detected, and the obtained level value is output to the power efficiency calculation unit 155.
  • the power efficiency calculation unit 155 calculates the power efficiency from the current value and the level value, and outputs the obtained power efficiency to the phase control signal generation unit 156.
  • the phase control signal generation unit 156 generates a phase control signal for controlling the phase of the variable phase shifter 140 so that the calculated power efficiency is maximized, and outputs the phase control signal to the variable phase shifter 140.
  • the constant envelope signal generation unit 110 generates two constant envelope signals SI (t) and S2 (t) from the input signal S (t), and the two constant envelope signals Sl (t) and S2 (t) is amplified by amplifiers 120-1 and 120-2, respectively.
  • the amplified constant envelope signals GX Sl (t) and GX S2 (t) are synthesized by the lossless synthesizer 130, and the resultant synthesized signal GXS (t) is output to the variable phase shifter 140.
  • the phase of the composite signal G X S (t) is controlled by the variable phase shifter 140 based on the phase control signal output from the phase control signal generation unit 156.
  • the phase control signal is output from the phase control signal generator 156 to the variable phase shifter 140 with reference to the power efficiency calculated by the power efficiency calculator 155.
  • the phase control signal will be described with reference to FIG.
  • FIG. 7 shows the correspondence between the power efficiency and the output load phase in the lossless combiner 130.
  • Fig. 7 shows the correspondence between ACLR and output phase.
  • the horizontal axis represents the load phase ([degree])
  • the left vertical axis represents power efficiency (PAE) ([%])
  • the right horizontal axis represents ACLR ([dB]).
  • the load phase is the value indicated by the triangle in FIG.
  • the ACLR measurement results are getting smaller at the load phase that maximizes power efficiency. For example, in Figure 7, when the output load phase is around 45 degrees, the power efficiency is maximized. When the output power load phase is 45 degrees, the ACLR also decreases.
  • the phase control signal for controlling the variable phase shifter 140 so as to maximize the power efficiency and shifting the output load phase is the phase control signal generator 15.
  • the two constant envelope signals Sl (t) and S2 (t) are amplified by the amplifiers 120-1 and 120-2, and the amplified GX Sl is amplified.
  • GX S2 (t) is synthesized by the lossless synthesizer 130, and the variable phase shifter 140 is controlled by the phase control signal output from the phase control signal generator 156, and the synthesized signal GXS The output load phase of (t) was controlled.
  • the variable phase shifter 140 is controlled so that the power efficiency calculated by the power efficiency calculation unit 155 is maximized.
  • FIG. 8 shows the main configuration of the transmitting apparatus according to the present embodiment.
  • the same components as in FIG. 4 are assigned the same reference numerals as those in FIG.
  • a vector control signal generator 157 is added to FIG. 4, and the vector adjusters 160-1 and 160-2 are respectively connected between the constant envelope signal generator 110 and the amplifiers 120-1 and 120-2. 2 is used.
  • Vector control signal generation section 157 generates a vector control signal based on the ACLR measurement result in ACLR detection section 151, and outputs the generated vector control signal to vector adjusters 160-1 and 160-2. To do. Specifically, the vector control signal generator 157 adjusts the vector adjusters 160-1 and 160-2 to obtain the combined signal GXS (t) of the two constant envelope signals SI (t) and S2 (t). The vector control signal is generated so that the measurement result of ACLR becomes smaller.
  • the vector adjusters 160-1 and 160-2 are vectors that are output from the vector control signal generation unit 157 as vectors of the two constant envelope signals SI (t) and S2 (t). Adjust based on the control signal.
  • the vector regulators 160-1 and 160-2 have two constant envelope signals Sl (t), The phase and amplitude of S2 (t) are adjusted.
  • the vector adjusters 160-1 and 160-2 are composed of, for example, a variable phase shifter or a variable attenuator.
  • the vector adjuster 160 before the two constant envelope signals Sl (t) and S2 (t) are amplified in the amplifiers 120-1 and 120-2. — 1, 160-2, and the vector control signal generator 157 adjusts the vectors of the two constant envelope signals Sl (t) and S2 (t) before synthesis by the ACLR detector 151.
  • the ACLR of the detected composite signal GXS (t) was made small. As a result, the phase errors and amplitudes of the two constant envelope signals can be adjusted to reliably eliminate the path errors of the two constant envelope signals after amplification. In addition, signal distortion can be further reduced.
  • FIG. 9 shows the main configuration of the transmitting apparatus according to the present embodiment.
  • the same components as in FIG. 4 are assigned the same reference numerals as in FIG. 4 and description thereof is omitted.
  • FIG. 9 is different from FIG. 4 in that a capacity control signal generation unit 158 is provided instead of the phase control signal generation unit 152, the lossless synthesizer 130 and the variable phase shifter 140 are deleted, and a synthesis unit 170 is added. Take the configuration.
  • FIG. 10 shows a main configuration of the synthesis unit 170.
  • the synthesizer 170 includes a path composed of a ⁇ 4 phase shifter 171-1 and a variable capacitance diode (varactor) 172-1 mounted from a lumped constant, and a lumped constant A ⁇ ⁇ 4 phase shifter 171-2 and a path composed of a variable capacitance diode (varactor) 172-2 are provided.
  • the variable capacitance diodes 172-1 and 172-2 are connected to the subsequent stage of the ⁇ 4 phase shifters 171-1 and 171-2, respectively.
  • the synthesizing unit 170 shown in FIG. 10 performs the circuit shown in FIG. 11, that is, ⁇ 4 phase shifter 1
  • a variable phase shifter 140 composed of a variable capacitance diode is provided after the lossless combiner 130 composed of 71-1, 171-2.
  • variable phase shifter 140 is configured by a variable capacitance diode, and instead of controlling the variable diode based on the ACLR measurement result in the ACLR detection unit 151, a lossless combiner 130 is implemented from lumped constant ⁇ ⁇ 4 phase shifter 171— 1, 1
  • Each of the ⁇ ⁇ 4 phase shifters 171– 1 and 171 2 is provided with variable capacitance diodes 172– 1 and 172– 2 to generate a capacitance control signal so that the ACLR measurement results are reduced. Based on the control signal output from the unit 158, the capacitance of the variable capacitance diodes 172-1, 172-2 is controlled.
  • capacitance control signal generation unit 158 Based on the ACLR measurement result in ACLR detection unit 151, capacitance control signal generation unit 158 has variable capacitance diode 1 in synthesis unit 170 so as to minimize the ACLR measurement result.
  • a control signal is generated to control the capacity of 72-1, 172-2, and the generated control signal is output to variable phase diodes 172-1, 172-2.
  • combining section 170 has ⁇ 4 phase shifters 171-1, 17
  • variable capacitance diodes 172-1 and 172-2 are installed in the subsequent stage of each ⁇ ⁇ 4 phase shifter 171–1, 171–2, so that the ACLR measurement result becomes small. Since the capacitances of the variable capacitance diodes 172-1 and 172-2 are controlled, the synthesis of the two constant envelope signals Sl (t) and S2 (t) and the adjustment of the output load phase are combined into one circuit. And the circuit scale can be reduced.
  • the combining unit 170 may be mounted from the combined phase shifters 173-1, 173-2. As a result, the synthesis unit 170 can be further reduced.
  • the capacitance control signal generation unit 158 has the variable capacitance diode 172 so that the power efficiency is maximized. — Generate control signal to control capacity of 1, 172— 2 Please do it.
  • One aspect of the transmission apparatus of the present invention includes: constant envelope signal generation means for generating first and second constant envelope signals from an input signal; and the generated first and second constant envelopes First and second amplifying means for amplifying the line signal respectively, combining means for combining the amplified first and second constant envelope signals to obtain a combined signal, and controlling the phase of the combined signal And a variable phase means.
  • the two constant envelope signals are generated from the input signal, the two constant envelope signals are amplified, and the two constant envelope signals after the amplification are combined to form the LINC method.
  • the synthesized signal which is the amplified signal for the input signal
  • the phase of the resulting synthesized signal can be controlled
  • signal distortion can be reduced by adjusting the output load phase of the synthesized signal. it can.
  • One aspect of the transmitting apparatus of the present invention is an acquisition unit that acquires an adjacent channel leakage power ratio of the composite signal after phase control by the variable phase unit, and the adjacent channel leakage power ratio is reduced.
  • a configuration is further provided that includes control means for controlling the phase of the variable phase means.
  • the phase of the combined signal can be controlled so as to reduce ACLR, and as a result, signal distortion can be reliably reduced.
  • One aspect of the transmission device of the present invention is a power efficiency calculation unit that calculates power efficiency of the transmission device, and a control that controls a phase of the variable phase unit so that the power efficiency is maximized. And means for further comprising.
  • the phase of the combined signal can be controlled so that the power efficiency is maximized.
  • signal distortion can be reduced while maximizing power efficiency and reducing ACLR.
  • One aspect of the transmission apparatus of the present invention is the first and second adjustment means for adjusting the first and second constant envelope signal vectors generated by the constant envelope signal generation means, Is further provided.
  • the phase and amplitude of the two constant envelope signals can be adjusted to eliminate the path error between the two constant envelope signals after amplification.
  • signal distortion can be reduced.
  • the combining means is implemented from a lumped constant.
  • variable phase means is composed of a variable capacitance diode connected to the subsequent stage of the ⁇ 4 phase circuit, and controls the phase of the composite signal by controlling the capacitance of the variable capacitance diode.
  • the transmission apparatus and transmission method of the present invention can reduce signal distortion while keeping the circuit scale small, and particularly to a transmission apparatus and transmission method for amplifying and outputting a transmission signal in wireless communication. Useful.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Amplifiers (AREA)

Abstract

La présente invention concerne un circuit amplificateur capable de réduire la distorsion du signal, tout en supprimant l'échelle de circuit. Dans cet appareil, les amplificateurs (120-1,120-2) amplifient deux signaux d'enveloppe constants (S1(t),S2(t)) et un système de combinaison sans perte (130) combine les deux signaux d'enveloppe constants (GxS1(t),GxS2(t)), tels qu'amplifiés. Une partie de génération de signal de commande de phase (152) génère un signal de commande de phase pour commander la phase de charge de sortie du signal combiné (GxS(t)) de sorte que l'ACLR du signal combiné (GxS(t)) à déterminer par une partie de détermination d'ACLR (151) soit réduit. Un décaleur de phase (140) commande, en fonction du signal de commande de phase, la phase de charge de sortie du signal combiné (GxS(t)).
PCT/JP2006/319992 2006-10-05 2006-10-05 Appareil et procédé de transmission Ceased WO2008044268A1 (fr)

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Cited By (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2011024598A1 (fr) * 2009-08-27 2011-03-03 京セラ株式会社 Circuit amplificateur de puissance électrique, et dispositif de transmission et dispositif de communication l'utilisant
WO2012086015A1 (fr) * 2010-12-21 2012-06-28 富士通株式会社 Dispositif d'amplification
JP2012531095A (ja) * 2009-06-18 2012-12-06 アルカテル−ルーセント 無線通信のための高効率送信機
AU2008279424B2 (en) * 2007-07-26 2013-06-13 Lexicon Pharmaceuticals, Inc. Methods and compounds useful for the preparation of sodium glucose co-transporter 2 inhibitors

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JP2001016044A (ja) * 1999-06-28 2001-01-19 Nec Network Sensa Kk 電力増幅装置
JP2003087129A (ja) * 2001-09-11 2003-03-20 Fujitsu Ltd 無線送信回路
JP2003152464A (ja) * 2001-11-13 2003-05-23 Shimada Phys & Chem Ind Co Ltd 歪補償送信増幅器
JP2003163607A (ja) * 2001-11-28 2003-06-06 Fujitsu Ltd 無線装置
JP2003298357A (ja) * 2002-03-29 2003-10-17 Shimada Phys & Chem Ind Co Ltd 電力増幅方法および電力増幅器
JP2005151290A (ja) * 2003-11-18 2005-06-09 Kokusai Denki Engineering:Kk 電圧制御可変移相器
JP2006203638A (ja) * 2005-01-21 2006-08-03 Sharp Corp 電力合成器、パワーアンプ、及び高周波通信装置

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Publication number Priority date Publication date Assignee Title
JP2001016044A (ja) * 1999-06-28 2001-01-19 Nec Network Sensa Kk 電力増幅装置
JP2003087129A (ja) * 2001-09-11 2003-03-20 Fujitsu Ltd 無線送信回路
JP2003152464A (ja) * 2001-11-13 2003-05-23 Shimada Phys & Chem Ind Co Ltd 歪補償送信増幅器
JP2003163607A (ja) * 2001-11-28 2003-06-06 Fujitsu Ltd 無線装置
JP2003298357A (ja) * 2002-03-29 2003-10-17 Shimada Phys & Chem Ind Co Ltd 電力増幅方法および電力増幅器
JP2005151290A (ja) * 2003-11-18 2005-06-09 Kokusai Denki Engineering:Kk 電圧制御可変移相器
JP2006203638A (ja) * 2005-01-21 2006-08-03 Sharp Corp 電力合成器、パワーアンプ、及び高周波通信装置

Cited By (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
AU2008279424B2 (en) * 2007-07-26 2013-06-13 Lexicon Pharmaceuticals, Inc. Methods and compounds useful for the preparation of sodium glucose co-transporter 2 inhibitors
JP2012531095A (ja) * 2009-06-18 2012-12-06 アルカテル−ルーセント 無線通信のための高効率送信機
WO2011024598A1 (fr) * 2009-08-27 2011-03-03 京セラ株式会社 Circuit amplificateur de puissance électrique, et dispositif de transmission et dispositif de communication l'utilisant
JPWO2011024598A1 (ja) * 2009-08-27 2013-01-24 京セラ株式会社 電力増幅回路ならびにそれを用いた送信装置および通信装置
WO2012086015A1 (fr) * 2010-12-21 2012-06-28 富士通株式会社 Dispositif d'amplification
US8686794B2 (en) 2010-12-21 2014-04-01 Fujitsu Limited Amplifying apparatus
JP5472488B2 (ja) * 2010-12-21 2014-04-16 富士通株式会社 増幅装置

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