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WO2007123045A1 - Convertisseur de puissance, procede de commande its et climatiseur - Google Patents

Convertisseur de puissance, procede de commande its et climatiseur Download PDF

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Publication number
WO2007123045A1
WO2007123045A1 PCT/JP2007/058085 JP2007058085W WO2007123045A1 WO 2007123045 A1 WO2007123045 A1 WO 2007123045A1 JP 2007058085 W JP2007058085 W JP 2007058085W WO 2007123045 A1 WO2007123045 A1 WO 2007123045A1
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WO
WIPO (PCT)
Prior art keywords
load
power supply
command value
idc
current
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Ceased
Application number
PCT/JP2007/058085
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English (en)
Japanese (ja)
Inventor
Hitoshi Haga
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Daikin Industries Ltd
Original Assignee
Daikin Industries Ltd
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Daikin Industries Ltd filed Critical Daikin Industries Ltd
Priority to AU2007242096A priority Critical patent/AU2007242096B2/en
Priority to US12/226,434 priority patent/US8269370B2/en
Priority to CN2007800054550A priority patent/CN101385224B/zh
Priority to EP07741521.4A priority patent/EP2009774B1/fr
Publication of WO2007123045A1 publication Critical patent/WO2007123045A1/fr
Anticipated expiration legal-status Critical
Ceased legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M5/00—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases
    • H02M5/40—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into DC
    • H02M5/42—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into DC by static converters
    • H02M5/44—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into DC by static converters using discharge tubes or semiconductor devices to convert the intermediate DC into AC
    • H02M5/453—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into DC by static converters using discharge tubes or semiconductor devices to convert the intermediate DC into AC using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M5/458—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into DC by static converters using discharge tubes or semiconductor devices to convert the intermediate DC into AC using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/12—Arrangements for reducing harmonics from AC input or output

Definitions

  • the present invention relates to a power converter and a control method thereof, and more particularly to a power converter of a type commonly called capacitorless and a control method thereof.
  • An air conditioner includes a motor for a refrigerant compressor and power conversion for supplying desired power to the motor.
  • a converter, an inverter, and a smoothing capacitor between them are used to convert power supplied from an AC power source.
  • a rear tuttle will be provided to improve the input power factor.
  • the rear tuttle capacity is about 2mH and the capacitor capacity is about 2000 ⁇ F.
  • Non-Patent Document 3 discloses a technique that omits the rear tuttle.
  • Non-Patent Document 1 Myint Ko Tun, 1 other, “New Type Sinusoidal Input UPS Controlled by DC Chopper Type Active Filter”, Annual Conference of Industrial Applications Division, IEEJ, Vol. III, IEEJ, 2002 August, p. 1301-1306
  • Non-Patent Document 2 Hiroshi Ito, 1 outside, “Capacitorless PWM Inverter”, Proc. Of the National Conference of Industrial Application Division, 1988, The Institute of Electrical Engineers of Japan, August 1988, p. 445-4 50
  • Non-Patent Document 3 Hitoshi Haga and 1 other, “Improvement of input current waveform of inverter for driving IPM motor without single phase electric field capacitor”, Proceedings of Annual Conference of Industrial Applications Division, 2002 I, 2002 8 Month, p. 415-418
  • the high-frequency interference can be suppressed by controlling the switching operation of the inverter.
  • it is necessary to increase the switching frequency of the inverter, for example, about ten times the resonance frequency. This is less desirable because it increases the switching loss in the inverter.
  • the present invention has been made in view of the above-described circumstances, and an object thereof is to suppress high-frequency interference to an AC power supply.
  • an input current (iul, ivl, iwl; ic) from an AC power source (1) is rectified, and a first power source line (21) and a second power source are rectified.
  • the switching power supply circuit (61; 62; 62) that operates to supply the second load (Cdc + Load; C2 + Load; 7) with the high-frequency component force of the first current with respect to the fundamental frequency of the input current. 6).
  • a second mode of power conversion according to the present invention is power conversion according to the first mode, wherein the switching power supply circuit (61; 62) is connected to the second power supply circuit from the switching power supply circuit.
  • the switching power supply circuit 61; 62
  • the switching power supply circuit 61; 62
  • the switching power supply circuit 62
  • the switching power supply circuit 61; 62
  • the switching power supply circuit 62
  • the second power supply circuit from the switching power supply circuit.
  • a third mode of power conversion according to the present invention is power conversion applied to the first mode, wherein the second load is a motor (7), and the switching power supply circuit (6 ) Is the deviation ( ⁇ ) of the rotational speed ( ⁇ ) of the motor with respect to its command value ( ⁇ *) and the first current ( — Switches (S31 to S36) that perform the switching operation according to the command value (iq *) obtained based on iL).
  • a fourth mode of power conversion according to the present invention is power conversion according to the first mode, wherein the switching power supply circuit (61; 62; 6) iL) and the second current (idc; idc; iq) flowing through the second load (Cdc + Load; C2 + Load; 7)! / the command value (v *; v *; vq *), the switches (SI, S2; SI, S2; S31 to S36) that perform the switching operation are provided.
  • an input current (iul, ivl, iwl; ic) from the AC power source (1) is rectified to rectify the first power source line (21) and the second power source (21).
  • a rectifier circuit (2) for outputting a DC voltage to the power line (22) and applying the DC voltage to the first load (4 + 5); the first power line and the second power line; Connected between the capacitor (Cd), the rear external loop (Ld) that forms a series resonant circuit with the capacitor, and connected between the first power line and the second power line, and applied to the rear tuttle.
  • Switching operation is performed with a duty based on the first voltage (vL) generated, and the second load is determined from the high-frequency component of the first current (one iL) flowing in the first power supply line with respect to the fundamental frequency of the input current.
  • a sixth aspect of the power variation that works for the present invention is a power variation that works for the fifth embodiment, and the switching power supply circuit (61; 62) is separated from the switching power supply circuit.
  • the switching power supply circuit 61; 62
  • the switching power supply circuit is separated from the switching power supply circuit.
  • ⁇ vO deviation of the output voltage (vO) applied to the second load (Cdc + Load; C2 + Load) with respect to its command value (vO *) and the first voltage (vL)
  • a switch (SI, S2) that performs the switching operation according to the obtained command value (idc *; idc *) is provided.
  • a seventh aspect of the power variation that works for the present invention is a power variation that works for the fifth embodiment, wherein the second load is a motor (7), and the switching power supply
  • the circuit (6) has a command value (iq *) determined based on a deviation ( ⁇ ) of the rotational speed ( ⁇ ) of the motor from the command value ( ⁇ *) and the first voltage (vL). ) To perform the switching operation (S31 to S36).
  • An eighth aspect of power conversion according to the present invention is power conversion according to the fifth aspect, in which the switching power supply circuit (61; 62; 6) has the first voltage (vL ) And the second negative Based on the second current (idc; idc; iq) flowing in the load (Cdc + Load; C2 + Load; 7)! /, And according to the command value (v *; v *; vq *)
  • a switch SI, S2; S1, S2; S31 to S36 for performing a switching operation is provided.
  • a ninth aspect of the power converter according to the present invention is the power converter according to any one of the second, third, sixth and seventh aspects, wherein the switch (SI, S2; S1, S2; S31 to S36) are the command value (idc *; idc *; iq *) and the second current (idc *) that flows to the second load (Cdc + Load; C2 + Load; 7).
  • the switching operation is performed according to the command value (V *; V *; vq *) obtained based on idc; iq).
  • a tenth aspect of power conversion according to the present invention is the power converter according to any one of the second to fourth and sixth to ninth aspects, wherein the first load ( 4 + 5) has a main load (5) and an inverter (4) that inputs the voltage across the capacitor (vdc) and outputs an alternating current (iu2, iv2, iw2) to the main load, The duty is determined by comparing the command value (idc; iq; V *; Vq *) with the carrier of the inverter (4).
  • An eleventh aspect of power conversion according to the present invention is a power converter that works in any one of the first to ninth aspects, wherein the first load (4 + 5) is: A main load (5) and an inverter (4) for inputting the voltage across the capacitor (vdc) and outputting an alternating current (iu2, iv2, iw2) to the main load.
  • the first load (4 + 5) is: A main load (5) and an inverter (4) for inputting the voltage across the capacitor (vdc) and outputting an alternating current (iu2, iv2, iw2) to the main load.
  • a first aspect of the air conditioner according to the present invention includes a power conversion applied to the eleventh aspect, a motor for a refrigerant compressor constituting the main load (5), and the second load. (Cdc + Load; C2 + Load; 7) and an air cooling fan, and air conditioning is performed by removing the latent heat of the refrigerant compressed by the refrigerant compressor by the fan.
  • the first aspect of the method for controlling the power variation that is useful for the present invention is that the input current (iul, ivl, iwl) of the AC power source (1) is rectified to rectify the first power line and the second power source. A DC voltage is output between the power line and the DC voltage is applied to the first load (4 + 5). Between the rectifier circuit (2) and the first power line and the second power line.
  • This is a method for controlling a power converter including a capacitor (Cd) to be connected and a switching power supply circuit (61; 62; 6) connected between the first power supply line and the second power supply line.
  • the switching power supply circuit to perform a switching operation with a duty based on a first current (one iL) flowing through the first power supply line, and Power is supplied to the second load (Cdc + Load; C2 + Load; 7) from a high frequency component with respect to the fundamental frequency of the input current.
  • a second aspect of the method for controlling power conversion according to the present invention is a method for controlling an electric power converter according to the first aspect, in which the switching power supply circuit (61; 62) 2 Based on the deviation ( ⁇ ⁇ ) of the output voltage ( ⁇ ) applied to the load (Cdc + Load; C2 + Load) from the command value ( ⁇ *) and the first current (-iL).
  • the switching power supply circuit is caused to perform the switching operation in accordance with the command value (idc *; id c *) determined in this way.
  • a third aspect of the power conversion control method according to the present invention is a power converter control method according to the first aspect, wherein the second load is a motor (7).
  • the command value (iq *) obtained based on the deviation ( ⁇ ) of the rotational speed ( ⁇ ) of the motor with respect to the command value ( ⁇ *) and the first current ( ⁇ iL)
  • the switching power supply circuit (6) performs the switching operation.
  • a fourth aspect of the power conversion control method according to the present invention is a power converter control method according to the first aspect, wherein the first current (one iL) and the first Based on the command value (v *; v *; vq *) obtained based on the second current (idc; idc; iq) flowing through the two loads (Cdc + Load; C2 + Load; 7)
  • the switching power supply circuit (61; 62; 6) is caused to perform the switching operation.
  • a fifth aspect of the power variation control method that is useful in the present invention is that the AC power source (1) power input current (iul, ivl, iwl) is rectified to rectify the first power source line and the second power source line. A DC voltage is output between the power line and the DC voltage is applied to the first load (4 + 5). Between the rectifier circuit (2) and the first power line and the second power line.
  • power input current iul, ivl, iwl
  • a capacitor (Cd) to be connected, a rear outer loop (Ld) that forms a series resonance circuit together with the capacitor, and a switching power supply circuit (61; 62) connected between the first power supply line and the second power supply line 6) is a method for controlling a power change comprising: causing the switching power supply circuit to perform a switching operation at a duty based on a first voltage (vL) applied to the rear tuttle, and causing the first power supply line to From the high-frequency component of the flowing first current (one iL) to the fundamental frequency of the input current, the second load (Cdc + Load; C2 + Load; 7) Provides a force.
  • a sixth aspect of the method for controlling power conversion according to the present invention is the same as that of the fifth aspect.
  • a method of controlling a force transducer which is applied from the switching power supply circuit (61; 62) to the second load ((1 + 1 + 1 ⁇ 0 &(1; 2 + 1 ⁇ 0 & (1))
  • the command value (idc *; idc *) obtained based on the deviation ( ⁇ ) of the output voltage ( ⁇ ) from the command value ( ⁇ *) and the first voltage (vL)
  • the power supply circuit performs the switching operation.
  • a seventh aspect of the power conversion control method according to the present invention is a power converter control method according to the fifth aspect, wherein the second load is a motor (7).
  • the switching speed according to the command value (iq *) obtained based on the deviation ( ⁇ ) of the rotational speed ( ⁇ ) of the motor from the command value ( ⁇ *) and the first voltage (vL).
  • the power circuit (6) is caused to perform the switching operation.
  • An eighth aspect of the power conversion control method according to the present invention is a power converter control method according to the fifth aspect, in which the first voltage (vL) and the second voltage are controlled. Based on the command value (v *; v *; vq *) obtained based on the second current (idc; idc; iq) flowing in the load (Cdc + Load; C2 + Load; 7)!
  • the switching power supply circuit (61; 62; 6) performs the switching operation.
  • the ninth mode of the power variation control method that is useful for the present invention is the second, third, sixth and seventh! ,
  • a control method of power variation ⁇ that works in one mode, wherein the command value (idc *; idc *; iq *) and the second load (Cdc + Load; C2 + Load; 7)
  • the switching power supply circuit (61; 62; 6) performs the switching operation according to a command value (v *; v *; vq *) determined based on the second current (idc; id c; iq) flowing through
  • a tenth aspect of the power conversion control method according to the present invention is a power converter control method according to any one of the second to fourth and sixth to ninth aspects.
  • the first load (4 + 5) receives the main load (5) and the voltage across the capacitor (vdc) and outputs an alternating current (iu2, iv2, iw2) to the main load ( 4), and the duty is determined by comparing the command value (idc; iq; v *; vq *) with the carrier of the inverter (4).
  • the second load consumes the high-frequency component included in the first current with respect to the fundamental frequency of the input current, so the high-frequency component of the input current to the rectifier circuit is suppressed and the high-frequency interference to the AC power supply is suppressed. To do.
  • the motor can be stably rotated.
  • the power consumption of the second load can be accurately controlled.
  • a tenth aspect of power conversion or a first method of controlling power conversion according to the present invention is a tenth aspect of power conversion or a first method of controlling power conversion according to the present invention.
  • the switching of the switching power supply circuit can be synchronized with the switching of the inverter.
  • the switching loss in the inverter is small.
  • the air cooling fan has lower power consumption and accuracy of rotation control than the refrigerant compressor motor. It is suitable for the control using the power converter which is effective in the aspect.
  • FIG. 1 is a diagram conceptually showing power conversion described in the first embodiment.
  • FIG. 2 is a diagram conceptually showing power conversion described in the first embodiment.
  • FIG. 3 is a diagram conceptually showing a control apparatus 10 for a power converter.
  • FIG. 4 is a graph showing an input current iul when the control described in the first embodiment is executed.
  • FIG. 5 is a graph showing a voltage vdc when the control described in the first embodiment is executed. 6] A graph showing the input current iul before executing the control described in the first embodiment.
  • FIG. 7 is a graph showing a voltage vdc before executing the control described in the first embodiment.
  • FIG. 9 is a diagram conceptually showing a power converter described in the second embodiment.
  • FIG. 10 is a diagram conceptually showing the power conversion control device 20.
  • FIG. 11 is a graph showing the input current iul when the control described in the second embodiment is executed.
  • FIG. 15 is a diagram conceptually showing power conversion described in the third embodiment.
  • FIG. 16 is a graph showing the input current ic when the control described in the third embodiment is executed.
  • ⁇ 20 This is a graph showing the input current ic when harmonic suppression is executed by inverter 4.
  • FIG. 21 is a graph showing the voltage vdc when harmonic suppression is performed in inverter 4.
  • the power converter includes a first power line 21, a second power line 22, a rectifier circuit 2, a capacitor Cd, a rear tuttle Ld, an inverter 4, and a switching power circuit 61 (or a switching power circuit 62).
  • FIGS. 1 and 2 show an AC power supply 1 that supplies power for the power conversion and a motor 5 that is supplied with an output from an inverter 4.
  • FIG. 1 the capacitor Cdc to which the output of the switching power supply circuit 61 is supplied and the drive unit Load are shown, and in FIG. 2, the capacitor C2 to which the output of the switching power supply circuit 62 is supplied and the drive unit Load are shown.
  • Capacitors Cdc and C2 smooth the outputs of the switching power supply circuits 61 and 62 and supply them to the drive unit Load.
  • a three-phase AC power source is employed as the AC power source 1.
  • the motor 5 is composed of a main load, a load composed of the motor 5 and the inverter 4 is a first load (denoted as “4 + 5” in the text), a capacitor Cdc, and a drive unit Load.
  • Load (Fig. 1) is the second load (denoted in the text as "Cdc + Load"), and the load consisting of capacitor C2 and drive section load (Fig. 2) is the second load (denoted as "C2 + And “Load”).
  • the rectifier circuit 2 is a bridge diode in the present embodiment, and rectifies the input currents iul, ivl, iwl from the AC power source 1 and between the first power source line 21 and the second power source line 22. Outputs DC voltage.
  • the capacitor Cd is connected between the first power supply line 21 and the second power supply line 22.
  • the rear tuttle Ld is provided on the first power supply line 21 between the rectifier circuit 2 and the capacitor Cd. Capacitor Cd and rear tuttle Ld form a DC resonant circuit.
  • Inverter 4 is a three-phase inverter in the present embodiment, and receives voltage vdc across capacitor Cd and outputs alternating currents iu2, iv2, and iw2 to motor 5.
  • the motor 5 is driven by the output of the inverter 4 being supplied.
  • Each of switching power supply circuits 61 and 62 is connected between first power supply line 21 and second power supply line 22.
  • the force connected to both ends of the capacitor Cd for example, may be connected to both ends of a series resonant circuit composed of the capacitor Cd and the rear tuttle Ld.
  • a step-down diode is used for the switching power supply circuit 61.
  • This step-down pressure switch has a switch SI, S2, a coin: Ldc and output terminals 611, 612.
  • the switches SI and S 2 are connected in series between the first power supply line 21 and the second power supply line 22.
  • Output terminals 611 and 612 are connected to both ends of switch S2, respectively.
  • the coil Ldc is connected in series with the switch S2 between the output terminals 611 and 612.
  • a second load Cdc + Load is connected between the output terminals 611 and 612.
  • a flyback converter is employed for the switching power supply circuit 62.
  • the flyback converter 62 has switches SI and S2, a transformer T, and output terminals 621 and 622.
  • the primary coil L1 of the transformer T is connected between the first power supply line 21 and the second power supply 22, and the secondary coil L2 is connected between the output terminals 621 and 622.
  • the switch S1 is connected in series with the coil L1 between the first power supply line 21 and the second power supply line 22.
  • the switch S2 is connected in series with the coil L2 between the output terminals 621 and 622.
  • a second load C2 + Load is connected between the output terminals 621 and 622.
  • an IGBT module composed of an IGBT (Insulated Gate Bipolar Transistor) and a diode is employed for the switches SI and S2.
  • FIG. 3 conceptually shows the control device 10 that controls the power converter shown in FIG.
  • the control device 10 includes subtractors 101 and 105, a command value correction unit 103, control units 102, 104, and 106, a triangular wave carrier generation unit 107, a comparison unit 108, and a NOT circuit 109.
  • the subtractor 101 obtains a deviation ⁇ of the output voltage ⁇ applied from the switching power supply circuit 61 to the second load Cdc + Load with respect to the command value ⁇ *.
  • the control unit 102 generates the command value idc * of the current idc flowing through the coil Ldc by executing PI control based on the deviation ⁇ . According to the powerful control, the voltage ⁇ can be brought close to the command value ⁇ *, so that the output voltage can be stably applied to the second load Cdc + Load. [0055]
  • the command value correction unit 103 corrects the command value idc * in which the switching power supply circuit 61 consumes the high frequency component of the current iL flowing through the first power supply line 21 with respect to the fundamental frequency of the input currents iul, ivl, iwl. To do.
  • command value correction unit 103 corrects command value idc * based on voltage vL applied to rear tuttle Ld. Specifically, the control unit 104 multiplies the voltage vL by the gain K1 to obtain the correction value A ide *, and the command value correction unit 103 subtracts the correction value A ide * from the command value idc *, and the result Is output as a new command value idc *.
  • the voltage vL is based on the potential on the rectifier circuit 2 side of the rear tuttle Ld.
  • phase of the correction command value ⁇ idc * may be shifted in accordance with the phase delay of the voltage vL in accordance with the phase delay.
  • the phase of Aide * may be delayed by 90 ° from the phase of voltage vL. This is because the phase of the current iL is delayed by 90 ° with respect to the phase of the voltage vL in the rear tuttle Ld.
  • the subtractor 105 obtains a deviation ⁇ idc between the corrected command value idc * and the current idc.
  • the control unit 106 generates a command value V * of the voltage V applied to both ends of the switch S2 by executing PI control based on the deviation Aide. According to the powerful control, the current idc can be brought close to the command value i dc *, so that the power consumption of the second load Cdc + Load can be accurately controlled.
  • the triangular wave carrier generation unit 107 generates a triangular wave carrier tuned to the inverter 4.
  • the comparison unit 108 compares the command value V * and the triangular wave carrier, and generates a switching command rl for the switch S1.
  • the switch S1 is controlled to be either on or off by the switching command rl. Since the switch S2 is controlled in a complementary manner to the switch S1, the command r2 for the switch S2 can be obtained by inputting the command rl to the NOT circuit 109.
  • the command values rl and r2 can be obtained by the control device 10, high-speed microcomputer processing is not necessary for controlling the switching power supply circuit 61.
  • the switching frequency of the inverter such as flyback converter or step-down chopper is higher than the switching frequency of inverter 4 (6kHz). Ching frequency (50-100kHz) can be increased.
  • the second load Cdc + Load can consume high-frequency components included in the current (one iL) with respect to the fundamental frequencies of the input currents 1, ivl and iwl. it can. Therefore, the high frequency components of the input currents iul, ivl, iwl to the rectifier circuit 2 can be suppressed, and the high frequency disturbance to the AC power source 1 can be suppressed.
  • FIG. 4 is a graph showing the change over time of the input current iul when the control that is relevant to the present embodiment is executed.
  • FIG. 5 is a graph showing the time change of the voltage vdc across the capacitor Cd when the control related to the present embodiment is executed.
  • the waveforms of the input current iul and the voltage vdc before executing the control according to the present embodiment are shown in FIGS. 6 and 7, respectively. Due to the series resonance between the rear tuttle Ld and the capacitor Cd, this waveform contains many high-frequency components.
  • the graphs in Figs. 4 to 7 show the command value ⁇ * [20V, Ma-ku Oad [This resistance, the power consumption of the second load Cdc +! Load [20W, 1.5 kW for the power consumption of the motor 5] It is a result obtained when adopting.
  • the switching power supply circuit 61 Since the high-frequency component of the power is smaller than the DC power supplied to the first load 4 + 5, the power consumption of the second load Cdc + Load that consumes this is the first load 4 + 5 It can be smaller than the power consumption. In view of this, it can be seen that high-frequency interference can be suppressed even when the power consumption of the switching power supply circuit 61 is small. Therefore, the current flowing through the switches SI and S2 of the switching power supply circuit 61 can be made smaller than the current flowing through the switching element of the inverter 4. That is, as compared with the switching in which the harmonics are controlled by the control in the inverter 4, the suppression force in the control in the switching power supply circuit 61 can be reduced. This makes it possible to use switches with small current capacity for switches SI and S2. Therefore, the switching power supply circuit 61 can be downsized.
  • the control device 10 can also be applied to the control of power conversion shown in FIG. However, instead of the current idc and its command value idc *, the current il flowing through the coil L1 and its command value il * are adopted.
  • the command value V * is the command value of the voltage across the coil L2.
  • the subtractor 105 and the control unit 106 may not be provided in the control device 10. In FIG. 8, a powerful mode is shown as the control device 11.
  • the control device 11 includes a subtractor 111, control units 112 and 114, a correction command value 113, a triangular wave carrier generation unit 115, a comparison unit 116, and a NOT circuit 117.
  • the subtractor 111 calculates the deviation ⁇ in the same manner as the subtractor 101 shown in FIG.
  • the control unit 112 generates the command value ⁇ * by executing the ⁇ control based on the deviation ⁇ .
  • the command correction unit 113 corrects the command value v * that the switching power supply circuit 61 should consume the high frequency component of the current iL flowing through the first power supply line 21 with respect to the fundamental frequency of the input currents iul, ivl, iwl. .
  • the control unit 114 multiplies the voltage vL by the gain K2 to obtain a correction value ⁇ , and the command value correction unit 113 subtracts the correction value ⁇ from the command value V * and obtains the result as a new command value. Output as V *.
  • phase of the correction command value ⁇ V * may be shifted in accordance with the phase delay of the voltage vL in accordance with the phase delay!
  • Triangular wave carrier generation unit 115 generates a triangular wave carrier tuned to inverter 4.
  • the comparison unit 116 compares the corrected command value V * with the triangular wave carrier, and generates a command value rl.
  • the command value r2 is obtained by the NOT circuit 117 in a complementary manner to the command value rl.
  • the high-frequency component with respect to the fundamental frequency of the input current 1, ivl, iwl included in the current (one iL) is also expressed by the second load Cdc + Load, C2 + Load by the powerful control device 11 and its control. Can be consumed. Therefore, the high frequency components of the input currents iul, ivl, iwl to the rectifier circuit 2 can be suppressed, and the high frequency interference to the AC power source 1 can be suppressed.
  • the voltage ⁇ in the present embodiment can be employed as a power supply voltage for electrical components used in a motor drive system for an air conditioner, a power supply voltage for controlling an inverter, or the like.
  • FIG. 9 conceptually shows the power converter according to the present embodiment.
  • the first power supply line 21, the second power supply line 22, the rectifier circuit 2, the capacitor Cd, the rear tuttle Ld, and the inverter 4 are configured in the same manner as the power converter of the first embodiment.
  • a switching power supply circuit 6 is connected between the first power supply line 21 and the second power supply line 22.
  • FIG. 9 shows an AC power supply 1 and a motor 5 as in FIGS. 1 and 2, and further shows a motor 7 to which the output of the switching power supply circuit 6 is supplied.
  • the motor 7 can be grasped as the second load with respect to the load composed of the inverter 4 and the motor 5 that is grasped as the first load 4 + 5.
  • the switching power supply circuit 6 is a three-phase inverter and includes switches S31 to S36.
  • IGBT modules are employed for the switches S31 to S36.
  • the three-phase inverter is controlled by microcomputer processing.
  • FIG. 10 conceptually shows a control device 20 that controls the power converter shown in FIG.
  • the control device 20 includes subtracters 201, 205, 207, a command value correction unit 203, control units 202, 204,
  • the subtractor 201 obtains a deviation ⁇ of the rotational speed ⁇ of the motor 7 with respect to the command value ⁇ *.
  • the control unit 202 generates a command value iq * for the q-axis current iq flowing through the motor by executing PI control based on the deviation ⁇ . According to the powerful control, the rotational speed ⁇ can be brought close to the command value ⁇ *, so that the motor 7 can be rotated stably.
  • the command value correction unit 203 corrects the command value iq * so that the switching power supply circuit 6 consumes high-frequency components with respect to the fundamental frequencies of the input currents iul, ivl, and iwl.
  • command value correction unit 203 corrects command value iq * based on voltage vL applied to rear tuttle Ld. Specifically, the control unit 204 multiplies the voltage vL by the gain K to obtain the correction value A iq *, and the command value correction unit 203 subtracts the correction value A iq * from the command value iq *. Is output as a new command value iq *.
  • the correction command value ⁇ iq * is adjusted according to the phase delay in the control unit 202 and the control unit 206 in which PI control is executed.
  • the phase may be shifted from the phase of voltage vL. Further, even when there is no phase delay in the control units 202 and 206, the phase of the correction command value A iq * may be delayed by 90 ° from the phase of the voltage vL.
  • the subtracter 205 obtains a deviation ⁇ iq between the corrected command value iq * and the q-axis current iq.
  • the control unit 206 generates a command value vq * of the q-axis voltage vq applied to the motor 7 by executing PI control based on the deviation A iq. With powerful control, the q-axis current iq can be brought close to the command value iq *.
  • the subtractor 207 obtains a deviation ⁇ id of the d-axis current id flowing through the motor 7 with respect to the command value id *.
  • the control unit 208 generates a command value vd * of the d-axis voltage vd applied to the motor 7 by executing PI control based on the deviation A id.
  • the d-axis current id can be brought close to the command value id *.
  • the power consumption of the motor 7 can be accurately controlled.
  • the conversion unit 209 converts the coordinates from the dq axis coordinate system to the three-phase coordinate system. Therefore, the command values vq * and vd * input to the conversion unit 209 are converted into the command values vu *, w * and vw * of the three-phase voltages vu, w and vw and output from the conversion unit 209.
  • the triangular wave carrier generation unit 210 generates a triangular wave carrier tuned to the inverter 4.
  • the PWM control unit 211 generates commands r31 to r36 for each of the switches S31 to S36, based on the command values vu *, w *, vw * and the triangular wave carrier.
  • the switch S31 and switch S34, the switch S32 and switch S35, and the switch S33 and switch S36 are complementarily controlled.
  • the motor 7 can consume high-frequency components with respect to the fundamental frequency of the input currents 1, ivl, and iwl included in the current (one iL). Therefore, high frequency components of the input currents iul, ivl, iwl to the rectifier circuit 2 can be suppressed, and high frequency interference to the AC power source 1 can be suppressed.
  • FIG. 11 is a graph showing the time change of the input current iul when the control according to the present embodiment is executed.
  • FIG. 12 is a graph showing the time change of the voltage vdc across the capacitor Cd when the control related to the present embodiment is executed.
  • the waveforms of the input current iul and the voltage vdc before executing the control according to the present embodiment are shown in FIGS. 13 and 14, respectively. . Due to the series resonance between the rear tuttle Ld and the capacitor Cd, this waveform contains many high-frequency components.
  • the graphs in Figs. 11 to 14 show the results obtained when the power consumption of motor 5 is 1.5 kW, the command value of motor 7 is ⁇ * ⁇ 500 rpm, and the output power of motor 7 is 20 W. .
  • the input current iul (and therefore the input currents ivl and iwl) are included in the voltage vdc by executing a powerful control. It can be seen that the high-frequency component that had been suppressed is suppressed.
  • the power consumption of the motor 7 is set to 20 W and that the power consumption of the motor 5 is about 1.5 kW
  • the power consumption of the switching power supply circuit 6 is small. It can also be seen that high-frequency interference can be suppressed. Therefore, switching loss in the switching power supply circuit 6 can be reduced. As a result, switches having a small current capacity can be employed for the switches S31 to S36. As a result, the switching power supply circuit 6 can be downsized.
  • the switching frequency of the inverter employed in the switching power supply circuit 6 is generally the same as the switching frequency (6 kHz) of the inverter 4. However, if the above control is performed by the switching power supply circuit 6, the switches S31 to S36 are switched at a switching frequency of about 50 kHz. Therefore, from the viewpoint of microcomputer processing, control by power conversion explained in the first embodiment is desirable. [0102] Third embodiment.
  • FIG. 15 shows a case where a single-phase AC power source is adopted as the AC power source 1 in the power converter shown in FIG.
  • the rectifier circuit 2 rectifies the input current ic from the AC power supply 1 and outputs a DC voltage between the first power supply line 21 and the second power supply line 22.
  • the rest of the configuration is the same as the power conversion shown in Fig. 1.
  • FIG. 16 is a graph showing a change over time of the input current ic when the control that is relevant to the present embodiment is executed.
  • FIG. 17 is a graph showing the time change of the voltage vdc when the control related to the present embodiment is executed.
  • waveforms of the input current ic and the voltage vdc before executing the control according to the present embodiment are shown in FIGS. Due to the series resonance between the rear tuttle Ld and the capacitor Cd, this waveform contains many high-frequency components.
  • FIG. 16 and FIG. 20 and a comparison between FIG. 17 and FIG. 21 show that the inverter 4 can also reduce the high frequency to the same extent as the control that is effective in this embodiment. However, since the switching frequency in the inverter 4 is increased, the switching loss is increased. 20 and 21 show the results obtained when the inverter is controlled at the switching frequency of 50 kHz to the switching frequency of the inverter 4.
  • the correction values Aide * and Aiq * input to the command value correction units 103 and 203 are based on the current (one iL) flowing through the first power supply line. May be calculated. [0110] This is because the switching power supply circuit 61, 62, 6 performs a switching operation with a duty based on the current (iL) flowing through the first power supply line 21, and the input current i ul of the current (one iL) , ivl, iwl, ic can be grasped as supplying power to the second loads Cdc + Load, C2 + Load, 7 from the high frequency components with respect to the fundamental frequency.
  • the present invention can be applied to the control of power fluctuation without the rear tuttle Ld, and the same effects as those of the first to third embodiments can be obtained.
  • the present invention can be applied to the control of power fluctuation without the rear tuttle Ld, and the same effects as those of the first to third embodiments can be obtained.
  • the present invention can be applied to the control of power fluctuation without the rear tuttle Ld, and the same effects as those of the first to third embodiments can be obtained.
  • harmonics are generated due to the series resonance between the impedance z generated between the AC power supply 1 and the rectifier circuit 2 and the capacitor Cd.
  • the subtracters 101, 111, 201 and the control units 102, 112, and 202 may be omitted. That is, the command values v * and vq * are obtained based on the voltage vL or current (-iL) and the currents idc and iq, and the switching power supply circuits 61, 62, and 6 are determined according to the command values v * and vq *. The switching operation may be controlled.
  • any of the voltage variations described above can be mounted, for example, in an air conditioner.
  • the air conditioner is provided with a motor for the refrigerant compressor and an air cooling fan, and the motor for the refrigerant pressure compressor has the output power of the inverter 4 and the switching power circuit 61, 62, Six outputs are each supplied.
  • Air conditioning is performed by removing the latent heat of the refrigerant compressed by the refrigerant compressor with a fan.
  • the air-cooling fan is smaller in both power consumption and rotation control accuracy than the refrigerant compressor motor. Therefore, control using a voltage converter is suitable for the air conditioner.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Inverter Devices (AREA)
  • Rectifiers (AREA)
  • Dc-Dc Converters (AREA)
  • Control Of Ac Motors In General (AREA)

Abstract

La présente invention concerne un convertisseur de puissance pour supprimer un problème de haute fréquence causé dans l'alimentation électrique CA. Un dispositif de commande (10) comprend des sous-traitants (101, 105), une unité de correction de valeur d'instruction (103) et une unité de commande (102). Le soustracteur (101) obtient une différence (Δv0) entre une tension de sortie (v0) appliquée à une seconde charge (Cdc + Load) à partir d'un circuit d'alimentation électrique de commutation (61) et sa valeur d'instruction (v0*). L'unité de commande (102) exécute la commande PI en fonction de la différence (Δv0) de manière à générer une valeur d'instruction (idc*) d'un courant (idc) circulant dans une bobine (Ldc). L'unité de correction de la valeur d'instruction (103) corrige la valeur d'instruction (idc*) de sorte que le circuit d'alimentation de commutation (61) consomme un composant haute fréquence du courant (iL) circulant dans une première ligne d'alimentation électrique (21) relativement à la fréquence de base des courants d'entrée (iu1, iv1, iw1). Le soustracteur (105) obtient une différence (Δidc) entre la valeur d'instruction (idc*) après la correction et le courant (idc). Selon la différence (Δidc), les instructions (r1, r2) au commutateur sont générées.
PCT/JP2007/058085 2006-04-19 2007-04-12 Convertisseur de puissance, procede de commande its et climatiseur Ceased WO2007123045A1 (fr)

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AU2007242096A AU2007242096B2 (en) 2006-04-19 2007-04-12 Power converter, its control method, and air conditioner
US12/226,434 US8269370B2 (en) 2006-04-19 2007-04-12 Power converter and its control method and air conditioner
CN2007800054550A CN101385224B (zh) 2006-04-19 2007-04-12 功率变流器及其控制方法、和空调机
EP07741521.4A EP2009774B1 (fr) 2006-04-19 2007-04-12 Convertisseur de puissance, procede de commande correspondant et climatiseur

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JP2006115814A JP4079178B2 (ja) 2006-04-19 2006-04-19 電力変換器及びその制御方法並びに空気調和機
JP2006-115814 2006-04-19

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US20090102285A1 (en) 2009-04-23
EP2009774B1 (fr) 2019-06-19
CN101385224B (zh) 2011-06-29
CN101385224A (zh) 2009-03-11
AU2007242096B2 (en) 2010-09-16
EP2009774A1 (fr) 2008-12-31
JP4079178B2 (ja) 2008-04-23
US8269370B2 (en) 2012-09-18
EP2009774A4 (fr) 2017-04-26
JP2007288971A (ja) 2007-11-01
AU2007242096A1 (en) 2007-11-01

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