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WO2000017992A1 - Alimentation a decoupage - Google Patents

Alimentation a decoupage Download PDF

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Publication number
WO2000017992A1
WO2000017992A1 PCT/EP1998/005957 EP9805957W WO0017992A1 WO 2000017992 A1 WO2000017992 A1 WO 2000017992A1 EP 9805957 W EP9805957 W EP 9805957W WO 0017992 A1 WO0017992 A1 WO 0017992A1
Authority
WO
WIPO (PCT)
Prior art keywords
power supply
output
voltage
transformer
rectifier diode
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Ceased
Application number
PCT/EP1998/005957
Other languages
German (de)
English (en)
Inventor
Lothar Heinemann
Jochen Mast
Franz-Jozef Moers
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
DaimlerChrysler Rail Systems Schweiz AG
Mercedes Benz Group AG
Alstom Transportation Germany GmbH
Original Assignee
ABB Daimler Benz Transportation Schweiz AG
DaimlerChrysler AG
ABB Daimler Benz Transportation Technology GmbH
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Priority to DE19711817A priority Critical patent/DE19711817A1/de
Application filed by ABB Daimler Benz Transportation Schweiz AG, DaimlerChrysler AG, ABB Daimler Benz Transportation Technology GmbH filed Critical ABB Daimler Benz Transportation Schweiz AG
Priority to JP2000571548A priority patent/JP2002526021A/ja
Priority to EP98950054A priority patent/EP1114505A1/fr
Priority to PCT/EP1998/005957 priority patent/WO2000017992A1/fr
Publication of WO2000017992A1 publication Critical patent/WO2000017992A1/fr
Anticipated expiration legal-status Critical
Ceased legal-status Critical Current

Links

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33561—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having more than one ouput with independent control
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0067—Converter structures employing plural converter units, other than for parallel operation of the units on a single load
    • H02M1/007—Plural converter units in cascade
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/01—Resonant DC/DC converters

Definitions

  • the invention relates to a switching power supply according to the preamble of claim 1.
  • the switching power supply according to the invention which separates very high potentials, can be used, for example, for IGBT gate drives of a traction-compatible IGBT converter for supplying a DC auxiliary power supply bus.
  • Switched-mode power supplies are usually dimensioned in such a way that a small volume, high reliability, good electromagnetic compatibility, high efficiency, high dynamics and the lowest possible price result. Furthermore, high insulation requirements are often to be observed, which complicate the technically good and at the same time inexpensive design of the power supply.
  • control signals for the primary and secondary switches are generated synchronized on the primary side using the same pulse voltage source.
  • additional potential isolation for the control signals is necessary, for example by means of an optocoupler or by means of a pulse transformer.
  • an optocoupler is to be regarded as disadvantageous due to the low reliability, the unfavorable drift behavior (poor long-term and temperature stability) as well as the high price and large volume, in particular with very high insulation voltages - more than 10 kV. For similar reasons, a pulse transformer can no longer be used efficiently with very high insulation requirements.
  • the invention has for its object to provide a switching power supply of the type mentioned, which meets very high insulation requirements - 10 kV and more - that generates the desired voltages with high precision and that is compact and simple.
  • the advantages that can be achieved with the invention are, in particular, that the number of relatively expensive, electrically isolating components is minimized in the proposed switched-mode power supply, because only a power-transmitting transformer is required as an electrically isolating component, while an optocoupler or pulse transformer for feedback of the controlled variable (generally one of the Output voltages) from the secondary to the primary side is not necessary.
  • an inexpensive, reliable switching power supply that is suitable for very high insulation requirements is created.
  • the high level of reliability can be explained by the small number of components in the power path and the simple, but effective electronics. Pulse-shaped component loads are avoided by soft current and voltage profiles. This also results in good electromagnetic compatibility of the switching power supply.
  • the cost-effectiveness is explained by the fact that the components of the power section are optimally electrical and be used thermally.
  • the secondary switch switches without loss.
  • the switching power supply has a very high efficiency.
  • the proposed PWM control it is completely irrelevant at what frequency the clocking on the primary side and how the control signals for the primary-side switch are formed (for example resonant mode controller, PWM controller or self-oscillating arrangement).
  • the proposed type of synchronization enables the power supply unit to be operated on the primary side with a variable switching frequency (frequency-modulated), which enables an additional degree of freedom in dimensioning - in particular with a wide input voltage range.
  • the PWM control which is synchronized on the secondary side, operates exactly frequency-synchronously with the control circuit of the primary-side switch. This has the following main advantages:
  • a change in the switching frequency depending on the input voltage can be implemented in a simple manner.
  • the frequency is increased as the input voltage increases, which has an extremely favorable effect on the efficiency of the power supply unit at high input voltages.
  • Such behavior is only possible with the use of the proposed control concept.
  • 1 shows the basic design of the switching power supply
  • 2 shows the time course of quantities of interest
  • FIG. 1 shows the basic design of the switching power supply. It is a zero voltage switched multi-resonance converter based on a flux converter.
  • a transformer TR1 can be seen, which is connected on the primary side to the input terminals 1a, 1b of the switching power supply via a series inductance LR and the parallel connection of a switch T1, an inverse diode D1 and a series capacitor Cs.
  • the transformer TR1 is the only link between the primary and the secondary side of the switching power supply.
  • the input terminals 1a, 1b are connected to an input capacitor Ci.
  • the DC input voltage Ui is present between these input terminals.
  • the transformer T1 is connected to a capacitor Cp on the secondary side.
  • the secondary AC voltage applied to the capacitor is designated Usek.
  • the series connection of a rectifier diode D3 and an output filter inductance LF1 lies between the positive output terminal 2a of the switching power supply and the secondary winding of the transformer.
  • the negative output terminal 2b of the switching power supply is connected directly to the secondary winding of the transformer TR1.
  • An output capacitor Ca1 is connected in parallel with the output terminals 2a, 2b.
  • the output DC voltage Ua1 is present between the output terminals 2a, 2b.
  • the parallel connection of a switch T2 and an inverse diode D2 lies between the connection point of the rectifier diode D3 with the output filter inductance LF1 and the negative terminal on the secondary side.
  • PWM pulse width modulation
  • Three function groups are used for this purpose, namely a synchronization 8, a pulse width modulator 9 and an inverter 10.
  • the synchronization 8 receives the secondary AC voltage Usek via its input terminals 3a, 3b and outputs corresponding synchronization signals to the input terminals 4a, 4b of the pulse width modulator 9.
  • the inverter 10 receives the DC output voltage Ua1 via its input terminals 6a, 6b and for this purpose forms inverse signals which are fed to the input terminals 5a, 5b of the pulse width modulator 9.
  • the pulse width modulator 9 controls the switch T2 via its output terminals 7a, 7b and, for this purpose, emits corresponding control signals UGS.
  • the secondary-side PWM control must work exactly frequency-synchronously to the control circuit of the primary-side switch T1.
  • the synchronization wins 8 synchronization signals which determine the correct point in time for the start of each new PWM switching period.
  • the zero crossing of the alternating voltage Usek on the secondary side very simply marks such a point in time and is therefore detected and used to generate a short synchronization pulse.
  • the inverter 10 detecting the DC output voltage Ua1 fulfills another important task. Since the P component of the controlled system is too large, the control amplifier must have a P component smaller than one to guarantee stability. This is not possible with a non-inverting basic circuit of the error amplifier of a PWM. In addition, the DC conditions must be taken into account, which are created by the internal determination of the controller reference voltage in the PWM chip. By inserting the inverter 10, it is advantageously possible to dimension the actual PID control amplifier conventionally.
  • the secondary PWM is controlled by the pulses obtained in the synchronization. It is important that the frequency of the pulse width modulator 9 in free-running operation is approximately 10% to 20% below the switching frequency of the switch T1 on the primary side. Then there is a perfect course of the ramp voltage causing the synchronization. As can easily be seen, the proposed purely secondary control system advantageously avoids the feedback of the controlled variable from the secondary to the primary side.
  • Fig. 2 shows the time course of quantities of interest, namely the secondary AC voltage Usek and the control signal UGS for the switch T1.
  • the switch T2 is closed in the period from t1 to t3.
  • the secondary AC voltage Usek has a zero crossing at time t2. Since the switch T1 is closed until the time t3, the alternating voltage Usek has the value zero in the period between t2 and t3.
  • the positive half-wave of the AC voltage Usek begins with a delay at time t3.
  • FIG. 2 also explains the control sense of the circuit according to FIG. 1. The longer the switch T1 remains closed due to the control signals UGS of the pulse width modulator 9, the lower the output voltage Ua1 formed from Usek.
  • FIGS. 3 and 4 show variants of how they are used to generate more than one DC output voltage.
  • an additional transformer TR2 with its primary winding is arranged between the connection point of the capacitor Cp with the rectifier diode D3 and the negative terminal.
  • the secondary winding of this transformer TR3 is connected on the one hand via a series circuit consisting of a rectifier diode D4 and an output filter inductance LF2 and on the other hand directly to further output terminals 11a, 11b of the switching power supply.
  • An output capacitor Ca2 is connected in parallel to these output terminals.
  • a diode D5 is connected between the connection point of the rectifier diode D4 with the output filter inductance LF2 and the negative terminal.
  • the DC output voltage Ua2 is present between the output terminals 11a, 11b.
  • the DC output voltage Ua2 is greater or less than the DC output voltage Ual
  • FIG. 3 shows a circuit for generating two different DC output voltages. Additional additional DC output voltages can be formed by connecting additional transformers in the same way. Furthermore, it is also possible to generate negative DC output voltages by inserting the rectifier diode D4 with reversed polarity.
  • the circuit shown in FIG. 4 is used to generate a positive DC output voltage Ua1 and a negative DC output voltage -Ua1 of the same amplitude.
  • the negative DC output voltage -Ua1 is present between further output terminals 12a, 12b of the switching power supply, the output terminal 12a being connected via a series connection of a rectifier diode D7 and an output filter inductance LF3 at the connection point of the rectifier diode D3 to the capacitor Cp, and the output terminals 12b directly to the negative output terminal 2b is connected.
  • An output capacitor Ca3 is connected in parallel to the output terminals 12a, 12b.
  • the parallel connection of a switch T3 with an inverse diode D6 is arranged between the connection point of the rectifier diode D7 with the output filter inductance LF3 and the negative output terminal 12b.
  • the switch T3 can in turn be controlled by the pulse width modulator 9.
  • circuits can be implemented which are based on combinations of the configurations shown in FIGS. 3 and 4.

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

L'invention concerne une alimentation à découpage comportant un transformateur (TR1) qui est relié côté primaire à un circuit produisant une tension avec un passage par zéro à chaque période, et qui, côté secondaire, est relié au montage en série d'une diode de redressement (D3) et d'une résistance inductive (LF1) de filtrage du courant de sortie. Le montage en parallèle d'un commutateur (R) et d'une diode inverse (D2) est situé entre le point de raccordement de la diode de redressement avec la résistance inductive (LF1) de filtrage du courant de sortie et l'autre borne côté secondaire. Un condensateur de sortie (Ca1) est prévu entre les bornes de sortie de l'alimentation à découpage (2a, 2b). Un modulateur d'impulsions en largeur (9) commande le commutateur (T2) en fonction de la tension continue de sortie (Ua1) et des passages par zéro de la tension côté primaire. Un organe de synchronisation (8) reçoit la tension alternative côté secondaire, appliquée aux bornes du transformateur (TR1), et produit des signaux de synchronisation correspondants pour le modulateur d'impulsions en largeur. Un convertisseur (10) reçoit la tension continue de sortie (Ua1) et l'achemine au modulateur d'impulsions en largeur, en l'inversant.
PCT/EP1998/005957 1997-03-21 1998-09-18 Alimentation a decoupage Ceased WO2000017992A1 (fr)

Priority Applications (4)

Application Number Priority Date Filing Date Title
DE19711817A DE19711817A1 (de) 1997-03-21 1997-03-21 Schaltnetzteil
JP2000571548A JP2002526021A (ja) 1998-09-18 1998-09-18 スイッチング電源
EP98950054A EP1114505A1 (fr) 1998-09-18 1998-09-18 Alimentation a decoupage
PCT/EP1998/005957 WO2000017992A1 (fr) 1997-03-21 1998-09-18 Alimentation a decoupage

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE19711817A DE19711817A1 (de) 1997-03-21 1997-03-21 Schaltnetzteil
PCT/EP1998/005957 WO2000017992A1 (fr) 1997-03-21 1998-09-18 Alimentation a decoupage

Publications (1)

Publication Number Publication Date
WO2000017992A1 true WO2000017992A1 (fr) 2000-03-30

Family

ID=26035079

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/EP1998/005957 Ceased WO2000017992A1 (fr) 1997-03-21 1998-09-18 Alimentation a decoupage

Country Status (2)

Country Link
DE (1) DE19711817A1 (fr)
WO (1) WO2000017992A1 (fr)

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
GB2358110A (en) * 2000-01-06 2001-07-11 Fujitsu Ltd Method for recognizing and recommending items of merchandise

Families Citing this family (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP1067664A1 (fr) * 1999-07-07 2001-01-10 TRT Lucent Technologies (SA) Régulateur répartiteur de tension pour une alimentation électrique
EP1067665A1 (fr) * 1999-07-07 2001-01-10 TRT Lucent Technologies (SA) Régulateur à découpage
DE10122534A1 (de) * 2001-05-09 2002-11-21 Philips Corp Intellectual Pty Resonanter Konverter
EP1257048B1 (fr) * 2001-05-09 2017-10-04 Philips Lighting Holding B.V. Dispositif de régulation pour convertisseur résonant
EP1303032A3 (fr) * 2001-09-04 2005-02-09 Philips Intellectual Property & Standards GmbH Dispositif de commande pour un convertisseur résonnant
CN109039089B (zh) * 2018-08-21 2024-06-04 珠海瑞捷电气股份有限公司 超宽电压输入的隔离开关电源

Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0475296A2 (fr) * 1990-09-07 1992-03-18 ANT Nachrichtentechnik GmbH Dispositif d'alimentation à découpage avec une sortie à convertisseur direct et une sortie à convertisseur à récupération
EP0605752A2 (fr) * 1993-01-05 1994-07-13 Yokogawa Electric Corporation Alimentation en courant commuté
WO1995008213A1 (fr) * 1993-09-13 1995-03-23 Melcher Ag Circuit de verrouillage actif
EP0696102A1 (fr) * 1994-08-01 1996-02-07 Siemens Aktiengesellschaft Convertisseur direct avec une circuit de sortie auxiliaire
US5568226A (en) * 1993-05-20 1996-10-22 Kusano; Akihisa Power supply device having control transistors connected in parallel with output voltage terminals

Family Cites Families (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE3712230C1 (en) * 1987-04-10 1988-10-20 Wandel & Goltermann DC voltage forward converter for a plurality of output voltages
FR2632134B1 (fr) * 1988-05-26 1990-09-14 Cachan Lesir Ecole Normale Sup Procede de linearisation pour convertisseur continu-continu et dispositifs mettant en oeuvre ce procede

Patent Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0475296A2 (fr) * 1990-09-07 1992-03-18 ANT Nachrichtentechnik GmbH Dispositif d'alimentation à découpage avec une sortie à convertisseur direct et une sortie à convertisseur à récupération
EP0605752A2 (fr) * 1993-01-05 1994-07-13 Yokogawa Electric Corporation Alimentation en courant commuté
US5568226A (en) * 1993-05-20 1996-10-22 Kusano; Akihisa Power supply device having control transistors connected in parallel with output voltage terminals
WO1995008213A1 (fr) * 1993-09-13 1995-03-23 Melcher Ag Circuit de verrouillage actif
EP0696102A1 (fr) * 1994-08-01 1996-02-07 Siemens Aktiengesellschaft Convertisseur direct avec une circuit de sortie auxiliaire

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
FARRINGTON R ET AL: "Constant-frequency zero-voltage-switched multi-resonant converters: analysis, design, and experimental results", PESC '90 RECORD. 21ST ANNUAL IEEE POWER ELECTRONICS SPECIALISTS CONFERENCE (CAT. NO.90CH2873-8), SAN ANTONIO, TX, USA, 11-14 JUNE 1990, 1990, NEW YORK, NY, USA, IEEE, USA, PAGE(S) 197 - 205, XP002100911 *

Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
GB2358110A (en) * 2000-01-06 2001-07-11 Fujitsu Ltd Method for recognizing and recommending items of merchandise
US6313745B1 (en) 2000-01-06 2001-11-06 Fujitsu Limited System and method for fitting room merchandise item recognition using wireless tag
GB2358110B (en) * 2000-01-06 2004-03-03 Fujitsu Ltd System and method for fitting room merchandise item recognition

Also Published As

Publication number Publication date
DE19711817A1 (de) 1998-09-24

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