RU2227272C2 - Wide-range fiber-optical meter of angular velocity - Google Patents

Abstract

FIELD: gyroscopic and instrumentation equipment. SUBSTANCE: wide-range fiber-optical meter of angular velocity incorporates optical circuit, device converting and extracting signal that forms train of pulses of specified duration and frequency proportional to speed from output of meter corresponding to sign of speed. Optical circuit of meter includes radiation source, depolarizer, input splitter, optical integrated circuit in the form of waveguide polarized and Y-shaped waveguide distributor with wide-band phase modulators on output arms, measurement fiber circuit and two photodetector modules connected in series by welding. To decrease random drift radiation source comes in the form of wide-range superlumeniscent diode, which is enveloped by two feedbacks. First feedback optically couples second output of radiation source to its input through photodiode of second photodetector module stabilizing by that radiation power by way of smooth change of pumping current of radiation source. Apart from this photodiode of second photodetector module is built into radiation source. Second feedback connects temperature-sensitive element (thermistor) to microcooler based on Peltier effect through amplifier controlling temperature which is bridge amplifier and power amplifier connected in series to stabilize temperature of radiation source by change of direction of current through microcooler. Microcooler and thermistor placed in feedback of bridge amplifier are built into radiation source. Device converting and extracting signal includes multichannel former of synchronization pulses, amplifier-converter of rectangular voltage, two phase-sensitive rectifiers, converter of rectangular voltage of auxiliary modulation, converter of saw-tooth voltage of compensation modulation, pulse converter whose main output is output of meter and source of secondary power supply. EFFECT: provision for stability and linearity of scale coefficient of wide-range fiber-optical meter of angular velocity in wide range of speeds, enhanced sensitivity and noise immunity, reduced random drift and weight of pulse without any effect on mass and size characteristics. 6 cl, 15 dwg

Description

The invention relates to gyroscopic and instrumentation and can be used in the development of fiber-optic angular velocity meters (VOIUS).

Similar VOIUS are described in the book of A. G. Sheremetev, Fiber Optic Gyroscope, M., Radio and Communications, 1987, pp. 40-43, 120-147, [1].

All-fiber VOIUS, made according to the minimal structure scheme, in the presence of auxiliary and compensating feedback, based on the built-in fiber-optic phase modulator, should provide a low level of random drift, high sensitivity and linearity of the output characteristic of VOIUS.

However, the level of random drift, sensitivity, stability and linearity of the VOIUS scale factor depends on temperature, overall mass characteristics and the range of the measured speed. In this case, a decrease in random drift is feasible, for example, by stabilizing the optical characteristics of the radiation source and using optical integrated circuits using thin-film waveguide technology. The circuitry solutions of the device for converting and isolating the components of the output signal generated at the output of the photodetector during interference of counterpropagating radiation waves can contribute to improving the sensitivity, stability, and linearity of the VOIUS scale factor.

The closest analogue in the set of essential features to the claimed technical solution is a Fiber-optic angular velocity meter (patent No. 2112927, G 01 C 19/72, publ. 10.06.98, Bull. No. 16).

This meter contains a sequentially optically coupled radiation source made in the form of a broadband superluminescent diode, a depolarizer, a radiation splitting-connection device made in the form of a sequentially optically coupled input splitter, polarizer and a contour splitter from a two-wire anisotropic single-mode fiber with preservation of polarization, and a measuring fiber circuit made of a single-core anisotropic single-mode fiber with conservation of polarization in the form of a coil with symmetrical winding relative to the middle of the total length with phase modulators of auxiliary and compensating modulation at the ends of the fiber circuit by winding the fiber onto the middle of the piezoceramic transducers with twist of each turn by π rad, the first photodetector module with differential output, photodiode, optically coupled to the third output of the input a splitter, the second output of which is optically coupled through a photodiode of the second photodetector module to the input of the radiation source, and the device generating and isolating a signal, the input of which is connected to the output of the first photodetector module, containing series-connected differential strip amplifiers with isolation capacitors at the differential outputs, a phase-sensitive rectifier and an analog-to-digital converter, the output of which is the output of the meter, as well as a secondary power source, an amplifier-converter high frequency sinusoidal voltage amplifier, low frequency and multi-channel sine wave voltage converter a shaper of synchronizing pulses, the phase-sensitive rectifier is made according to a double synchronous detection scheme and contains a summing integrator with two synchronous detectors connected to its inputs, each sinusoidal voltage amplifier-converter contains a series-connected integrator circuit, one of the inputs of which is an input of an amplifier-converter a modulator and a strip amplifier, the output of which is the output of the amplifier-converter, covered by the negative feedback, including a rectifier, and the outputs of the synchronizing pulse generator are connected to the control inputs of the analog-to-digital converter, synchronous detectors of a phase-sensitive rectifier, modulators and rectifiers of high and low frequency sinusoidal voltage converters, the outputs of which are connected to phase modulators of auxiliary and compensating modulation, respectively and the input of the low-frequency sinusoidal voltage converter amplifier is connected to the next output of the phase-sensitive rectifier, while the synchronizing pulses on the control inputs of the phase-sensitive rectifier have a duration of less than half a period and are shifted relative to each other by an odd number of half-periods of the frequency of the modulating signal of the auxiliary modulation phase modulator, and the frequency of the modulating signal of the phase modulator of compensating modulation is much smaller and a multiple of the frequency of the modulating signal phase modulator auxiliary modulation.

The main drawback of the described VOIUS is an unacceptable level of error of the scale factor when expanding the range of measurement of angular velocity.

The task of the invention is to reduce the level of error of the scale factor of small-sized wide-band VOIUS. The task is carried out as follows.

In VOIUS, containing a measuring fiber circuit made of a single-core anisotropic single-mode fiber with polarization in the form of a coil with symmetrical winding relative to the middle of the total length, a radiation source made in the form of a broadband superluminescent diode, a depolarizer, a splitting-coupler, two photodetector modules, phase auxiliary and compensating modulation modulators, a signal conversion and isolation device including a multi-channel sync driver pulses, the first phase-sensitive rectifier with two control inputs, a pulse converter, one of the outputs of which is the output of the meter, and a secondary power source, while the first phase-sensitive rectifier is made according to the double synchronous detection scheme in the form of a summing integrator, to the inputs of which two synchronous detectors are connected the control inputs of which are connected to the outputs of the shaper of synchronizing pulses, and the synchronizing pulses to the control input Axes of the first phase-sensitive rectifier have a duration of less than half a period and are shifted relative to each other by an odd number of half periods of the auxiliary modulation frequency, a thermistor and a micro-cooler based on the Peltier effect are integrated into the radiation source with a photodiode of the second photodetector module, a temperature control amplifier made in the form of a series-connected bridge amplifier (book of B.K. Nesterenko. Integrated Operational Amplifiers, Moscow: Energoizdat, 1982, Fig. 27c, p. 41, [2]), with a thermistor in feedback, and a power amplifier connected to a microcooler, the splitting-connection device is made in the form of an input splitter and an optical integrated circuit (a book by T. Okosi et al. Fiber Optic Sensors. L .: Energoizdat, 1990, pp. 126-130, [3]), containing a waveguide polarizer and a Y-shaped waveguide distributor, the output arms of which include broadband phase modulators optically coupled to with a fiber-optic circuit, the first output of the radiation source is optically coupled through a depolarizer to the input of the input splitter, the first output of which is optically connected to the waveguide polarizer, the second output of the input splitter is optically connected through a segment of a multimode fiber with a photodiode of the first photodetector module with a differential output and an isolation capacitor at the differential inputs ( The book by J. Ash and others. Sensors of measuring systems, M.: Mir, 1992, p.168, [4], book by P. Horwitz, W. Hill, The Art of Circuit Engineering, vol. 1, M., Mir, 1983, p. p.451, [5]), the second output of the radiation source is optically connected through the photodiode of the second photodetector module to its input, and a rectangular voltage amplifier with differential output, made according to the double synchronous detection scheme with one control input in the form of two differential amplifiers with isolation capacitors at the differential inputs, second phase connected in series through synchronous detectors (p. 397, [5]) a sensitive rectifier with two control inputs and an input, through a separation capacitor connected to one of the differential outputs of the amplifier-converter of rectangular voltage, a rectangular voltage converter of auxiliary phase modulation with two control inputs, the main input connected to the output of the second phase-sensitive rectifier, and an additional input - with the output of the secondary power source, sawtooth voltage converter compensating phase modulation with dv knowing the control inputs and through the first phase-sensitive rectifier, with isolation capacitors at the input, connected to the output of the rectangular-voltage amplifier-converter, while according to the differential output circuit, the output of the auxiliary phase-modulation rectangular-voltage converter is connected to the main output of the sawtooth-voltage converter of compensating phase modulation through parallel broadband phase modulators of auxiliary and compensation connected by a push-pull circuit modulating voltage, the auxiliary outputs of the auxiliary voltage phase-voltage converter, are connected to the symmetrical reference inputs of the pulse converter, the additional reference input of the secondary power supply connected to the output, and the main input of the compensating phase-modulated sawtooth voltage converter connected to the additional output, the control inputs are connected to two additional pulse outputs converter, multi-channel output The synchronization pulse generator is connected to the control inputs of the synchronous detectors of the rectangular-voltage amplifier-converter and the second phase-sensitive rectifier, as well as to the control inputs of the switches of the rectangular-voltage converter of auxiliary phase modulation and the secondary power supply control circuit, while the clock pulse on the control input of the rectangular-voltage amplifier-converter has less than the time it takes to go around the light of the measuring fiber con Hurray with a repetition interval equal to the clock offset at the control inputs of synchronous detectors of phase-sensitive rectifiers and half the duration of the sync pulse at one of the control inputs of the auxiliary voltage converter of phase auxiliary phase modulation with a repetition interval equal to the repetition interval of sync pulses at the control inputs of the second phase-sensitive rectifier, two sync at the second control input of the rectangular voltage converter The auxiliary phase modulation has a repetition interval equal to the frequency period of the auxiliary phase modulation, a multiple of the repetition interval of the clock pulses at the control inputs of the phase-sensitive rectifiers.

The second phase-sensitive rectifier can be made according to the double synchronous detection scheme in the form of an integrating adder-subtractor (Fig. 26a, p. 39, [2]) connected to the rectifier input with an inverting input through two parallel-connected synchronous detectors and a non-inverting input through a passive filter while the output of the adder-subtractor is the output of the second phase-sensitive rectifier.

The auxiliary phase modulation rectangular voltage converter may contain a circuit of series-connected summing amplifier, the inputs of which are the inputs of the converter, and an inverter, the outputs of which are additional outputs of the converter and connected to the inputs of two series-parallel switches (book by W. Titze, K. Schenk. Semiconductor circuitry, M .: Mir, 1983, Fig. 17.1c, p. 276, [6]) with voltage dividers at one of the inputs, and the outputs of the switches, the control input of which is is the first control input of the converter, connected to the inputs of the third series-parallel switch, the control input of which is the second control input of the converter, and the output is the main output of the converter.

The compensating phase modulation sawtooth voltage converter may include an integrator with variable slope, in which one of the input series-connected resistors is shunted by diodes, and the integrating capacitor is shunted by a key, the control input of which is one of the control inputs of the converter, and the input resistor circuit through the serial-parallel input a switch with an inverter at one of the inputs is connected to the input of the converter, the additional output of which is Exit integrator, and the main output - additional output switch in series-parallel with the inverter on one of its inputs connected through termokompensiruyuschy amplifier output of the integrator, wherein the control input of the switches is a second control input of the inverter.

The pulse converter can be made in the form of a unified self-adjusting device containing comparators, RS-flip-flops, D-flip-flops and two-input logic elements OR-NOT, AND-NOT, while the first RS-trigger (memory cell) is connected by inputs to the outputs of the first and second comparators, the first inputs of which are connected to the first input of the third comparator and are the main input of the converter, the first input of the fourth comparator is connected through RC circuits with the outputs of the first and second comparators, the second inputs of which I symmetric reference inputs of the converter, the second input of the third comparator is connected to a common bus, and the second input of the fourth comparator is an additional reference input of the converter, one of the additional outputs of which is the output of the fourth comparator connected to the clock input of the first D-trigger (frequency divider), the second RS-trigger (memory cell) inputs connected to the main outputs of the second and fifth D-trigger (pulse shapers of a given duration), the third RS-trigger (memory cell) input they are connected to the main outputs of the third and fourth D-flip-flops (pulse shapers of a given duration), while the clock inputs of the second and third D-flip-flops are connected to the outputs of the first RS-flip-flop, the clock input of the fourth D-flip-flop is connected to the output of the third comparator connected to clock input of the fifth D-flip-flop through the first, with double inputs, the OR-NOT element, the inverse outputs of the second and third D-flip-flops are connected to the inputs of the first AND-NOT element, the output connected to one of the inputs of the second OR-NOT element, w the input connected to the output of the second AND-NOT element, the inputs connected to the output of the third and fourth AND-NOT element, while the inputs of the third AND-NOT element are connected to one of the outputs of the third RS-trigger and to the main output of the fifth D-trigger, and the inputs of the fourth AND-NOT element are connected to one of the outputs of the second RS-trigger and to the main output of the fourth D-trigger, the output of the second OR-NOT element is connected to one of the inputs of the third and fourth OR-NOT element, the outputs of which are the output of the converter, and second inputs connect terms to the outputs of the first D-trigger connected to one of the inputs of the fifth and sixth OR-NOT element, the second inputs connected to the outputs of the first RS-trigger, and the outputs to the inputs of the seventh OR-NOT element, the output of which is the second additional output of the converter, the first and third RS-flip-flops are made of two elements OR NOT the first inputs of which are covered by cross-connections, and the second inputs are inputs of RS-flip-flops, the second RS-flip-flop is made on the basis of the D-flip-flop, which controls the inputs connected to the common bus.

The proposed wide-range VOIUS differs from the prototype in that the output of the radiation source is optically connected by the first feedback to its input through a second photodetector module integrated into the source of the photo diode, in addition, the radiation source is covered by a second feedback containing a temperature sensor (thermistor) connected to the microcooler ( based on the Peltier effect) through a thermal control amplifier in the form of a series-connected bridge amplifier and a power amplifier, with a micro-cooler and a thermistor, including The feedback amplifier of the bridge amplifier is integrated into the radiation source, the splitting-connection device is made in the form of an input splitter and an optical integrated circuit containing a waveguide polarizer and a Y-shaped waveguide distributor, the output arms of which include broadband (w / n) phase modulators, optically coupled to a measuring fiber circuit with a long fiber L≤C / 2fn, where C is the speed of light in vacuum, n is the refractive index of the fiber, f <l / 2r is the signal frequency of the auxiliary phase module rectangular, r is the time by which the light passes around the measuring circuit, while the second output of the input splitter is optically coupled through a segment of a multimode fiber with a photodiode, with the bias voltage applied back to the first photodetector module with isolation capacitors at the differential inputs, to the signal conversion and isolation device a rectangular-voltage amplifier-converter with differential output, implemented according to the scheme of double synchronous detection with one a control input in the form of two differential amplifiers sequentially connected through synchronous detectors with isolation capacitors at the differential inputs, a second phase-sensitive rectifier with two control inputs, an input through a separation capacitor connected to one of the differential outputs of the rectangular voltage amplifier-converter, an auxiliary phase modulation rectangular voltage converter with two control inputs, connected by the main input to the output one phase-sensitive rectifier and an additional input - with the output of the secondary power supply, a sawtooth voltage converter of compensating phase modulation with two control inputs, connected by an input through the first phase-sensitive rectifier with isolation capacitors at the input, with the output of the rectangular-voltage amplifier-converter, in this case, with differential output, the main output of the converter of rectangular voltage auxiliary phase modulation is connected to the main the output of the sawtooth voltage converter of compensating phase modulation through the broadband phase modulators of auxiliary and compensating modulation parallel-connected in a push-pull circuit, the additional outputs of the rectangular phase voltage converter of the auxiliary phase modulation are connected to the symmetrical reference inputs of the pulse converter, an additional reference input connected to the output of the secondary power source and the main input connected to the auxiliary output pre a compensating phase-modulated ramp voltage generator, the control inputs connected to two additional outputs of the pulse converter, the outputs of the multi-channel synchronizing pulse shaper are connected to the control inputs of the synchronous detectors of the rectangular voltage amplifier-converter and the second phase-sensitive rectifier, as well as to the control inputs of the switches of the rectangular phase voltage converter of the auxiliary phase modulation and source of secondary n at the same time, the sync pulse at the control input of the rectangular-voltage amplifier-converter has a duration shorter than the time it takes for the light to bypass the measuring fiber circuit with a repetition interval equal to the shift of the clock pulses at the control inputs of phase-sensitive rectifiers and less than the sync pulse at the first control input of the square-wave converter of auxiliary phase modulation with an interval sequence equal to the interval following the clock on the control inputs of the second the first phase-sensitive rectifier, the synchronous clock duty cycle square wave type 2 at the second control input of the auxiliary converter rectangular voltage phase modulation has a repetition interval equal to the period of the auxiliary frequency phase modulation, multiple repetition interval to the sync control input of phase-sensitive rectifiers.

A positive result of the invention is to reduce the level of error of the scale factor in a wide range of speeds by applying an optical integrated circuit with broadband phase modulators, choosing the optimal length of the measuring fiber circuit and the frequency of the phase modulation, as well as circuitry solutions in terms of improving the signal-to-noise ratio, compensating for phase drift shifts of radiation and stabilization of power and temperature of the radiation source.

The proposed WOIUS provides interconnection with governing bodies and meets the general safety requirements.

The set of essential features of the claimed device in the search for known technical solutions in science and technology is not found.

The invention is illustrated by the schemes shown in Fig.1-15.

Figure 1 shows the structural diagram of VOIUS, which includes a sensitive element containing a radiation source 1, a depolarizer 2, an input splitter 3, an optical integrated circuit 4 containing a waveguide polarizer P and a Y-shaped waveguide distributor with broadband phase modulators FM1 and FM2 on the output arms , measuring fiber circuit (NEC) 5, the first photodetector module 6, connected by welding C1-C6, a signal conversion and signal extraction device containing a multi-channel synchronizer pulses 7, a rectangular-voltage amplifier (PE) 8, a first phase-sensitive rectifier (FIV) 9, a second phase-sensitive rectifier 10, a rectangular voltage converter of auxiliary phase modulation 11, a sawtooth voltage converter of compensating phase modulation 12, a pulse converter 13 and a secondary power supply 14 , a device for stabilization of radiation power, containing a second photodetector module 15, the output connected to the source 1, and the input with a built-in source 1 photo diode, a temperature stabilization device containing a thermoregulation amplifier 16, connected to a micro-cooler integrated with a temperature sensor in the source 1 by the output.

Figure 2 shows the circuit diagram of the first photodetector module 6.

Figure 3 shows the functional diagram of a multi-channel shaper of synchronizing pulses 7.

Figure 4 shows the functional diagram of the amplifier-Converter rectangular voltage 8.

Figure 5 shows the functional diagram of the first phase-sensitive rectifier 9.

Figure 6 shows the functional diagram of the second phase-sensitive rectifier 10.

Figure 7 shows the functional diagram of the Converter rectangular voltage auxiliary phase modulation 11.

On Fig shows a functional diagram of the Converter sawtooth voltage compensating phase modulation 12.

Figure 9 shows the circuit diagram of the integrator FROM the Converter 12.

Figure 10 shows the functional diagram of the pulse Converter 13.

Figure 11 shows a circuit diagram of a second photodetector module 15.

Figure 12 shows a circuit diagram of a thermal control amplifier 16.

On Fig shows a timing diagram of the operation of WOIUS.

On Fig shows a timing diagram of the operation of VOIUS when deviating the slope of the phase modulators FM1 and FM2.

On Fig shows a timing diagram of the operation of the pulse Converter 13.

When measuring the angular velocity by forming phase shifts of counterpropagating radiation in the optical circuit, interfering with the radiation and converting the radiation intensity increment into an electrical signal in the form of a train of pulses of a given duration and frequency proportional to the speed corresponding to the direction of IP13 output, the proposed VOIUS works as follows.

The radiation of source 1 (Fig. 1) passes through a series of optically coupled depolarizer 2 and an input splitter 3 to the optical integrated circuit 4, where the polarizer P passes and is split by a Y-shaped waveguide distributor into two radiation equal in intensity, counter propagating in IVK5 and modulated, with opposite phase shifts, modulators FM1 and FM2.

In the presence of a signal V _in (1, Fig. 13) from the main output of FDA11 (Fig. 7), the counterpropagating emissions that have passed during the time of the IVK5 circuit have phase shifts at its output (2 and 3, Fig. 13). Then the oncoming radiation is re-modulated and has phase shifts (4 and 5, Fig.13). If there is a calculated amplitude of phase shifts (2 and 3, Fig. 13) between counterpropagating emissions, the total phase difference Δφ (6, Fig. 13) has (up to time t ₁ ) the form of the sum of two sequences of short-duration pulses of the opposite sign with an amplitude of π / 2 rad , duration τ and signal frequency V _in (1, Fig. 13), while the shift between pulses of the opposite sign is equal to the half-period of the voltage frequency of the auxiliary phase modulation. Moreover, to monitor the steepness of the phase modulators, the amplitude of the phase shifts (2-5, Fig.13) periodically briefly increases three times.

In the presence of the Sagnac phase Δφ _s (moment t ₁ ), the total phase difference Δφ (6, Fig.13) has a component corresponding to the sign and proportional to the measured speed.

After interference of counterpropagating emissions in a Y-shaped waveguide distributor, the increase in radiation intensity (7, Fig. 13) at the second output of splitter 3 is proportional to COS Δφ and has the form of alternating levels. Moreover, up to the moment t ₁ we have a sequence of short-term levels equal to zero, and in the interval from the moment t ₁ to the moment t ₂ (the moment of full compensation of the Sagnac phase) we have a sequence of short-term levels other than zero. From time t _{2, the} total phase difference Δφ (6, Fig. 13) and the intensity increment (7, Fig. 13) are similar to the sequences of levels up to time t ₁ .

Conversion of the radiation intensity increment (7, Fig. 13) into an electrical signal V $\genfrac{}{}{0ex}{}{\text{+}}{\text{fm}}$ and v $\genfrac{}{}{0ex}{}{\text{-}}{\text{fm}}$ carried out by the first photodetector module 6 (Figure 2). Subsequent conversion of balanced V signals $\genfrac{}{}{0ex}{}{\text{+}}{\text{fm}}$ and v $\genfrac{}{}{0ex}{}{\text{-}}{\text{fm}}$ , similar (7, Fig.13) is carried out using the clock pulses F1-F8 (8-15, Fig.13), supplied to the control inputs of the functional nodes of the device for converting and isolating the signal from the outputs of the generator of synchronizing pulses 7 (Fig.3).

The sync pulse F1 (8, Fig. 13), applied to the control input of synchronous detectors of the rectangular-voltage amplifier-transformer 8 (Fig. 4), has a duration shorter than the time τ bypassing the light of the measuring circuit 5. The interval of repetition of the sync pulse F1 (low-level interval at normal closed contacts of synchronous detectors D1 and D2) is equal to the shift between the clock pulses Ф2 (9, Fig.13) and Ф3 (10, Fig.13) supplied to the control input of synchronous detectors D3 and D4 of the first phase-sensitive rectifier 9 (Fig.5), and exactly odd the number of half periods (one half period in Fig. 13) of the signal frequency V _in (1, Fig. 13) from the main output of the FDA 11 (Fig. 7).

The frequency of the clock pulses Ф2 (9, Fig.13), Ф3 (10, Fig.13), Ф4 (11, Fig.13) and Ф5 (12, Fig.13) is multiple, and the duration is less than half the period of the signal frequency V _in (1, Fig.13). In this case, the shift of the clock pulses F4 (11, Fig.13) and F5 (12, Fig.13) supplied to the control input of the synchronous detectors D5 and D6 of the second phase-sensitive rectifier 10 (Fig.6) is less than the duration of the low level of the clock pulse F6 (13, Fig. 13) supplied to the control input of a dual series-parallel switch 1K of the FDA converter 11 (Fig. 7). The repetition rate of the low level of the F6 clock pulse (13, Fig. 13), applied to triple the increase in the amplitude of the phase shifts (2 and 3, Fig.13), is a multiple of the repetition rate of the F7 and F8 clock pulses (14 and 15, Fig.13) of the meander type ”Duty cycle 2 at the control input of the serial-parallel switch 2K of the FDA converter 11 (Fig. 7) and the control circuit of the IWP 14 (Fig. 1).

Thus, when applying the clock pulse F1 (8, Fig.13) to the control input UP 8 (Fig.4), the synchronous detectors D1 and D2 carry out “sampling-storage” of the variable component of the increment of radiation intensity (7, Fig.13). At the balanced outputs of UP8, V signals are formed $\genfrac{}{}{0ex}{}{\text{+}}{\text{up}}$ (16, FIG. 13) and V $\genfrac{}{}{0ex}{}{\text{-}}{\text{up}}$ (17, Fig. 13) with an amplitude proportional to SIN (Δφ _c -Δφ _k ) and a frequency equal to the frequency of the signal V _in (l, Fig. 13).

When applying the clock pulses F2 (9, Fig.13) and F3 (10, Fig.13) to the control inputs of the first phase-sensitive rectifier PSF 9 (Fig.5) synchronous detectors D3 and D4 are carried out through the separation capacitors “sampling-storage” of the V signals $\genfrac{}{}{0ex}{}{\text{+}}{\text{up}}$ (16, FIG. 13) and V $\genfrac{}{}{0ex}{}{\text{-}}{\text{up}}$ (17, Fig. 13), respectively. At the same time, at the inverting input of the integrator I1 (Figure 5), the signals from the output of the detector D3 (18, Fig. 13) and the detector D4 (19, Fig. 13) are summed.

When applying the clock pulses F4 (11, Fig.13) and F5 (12, Fig.13) to the control inputs of the second phase-sensitive rectifier PSF 10 (Fig.6) synchronous detectors D5 and D6 are carried out through a separation capacitor “sampling-storage” signal V $\genfrac{}{}{0ex}{}{\text{-}}{\text{up}}$ (16, Fig. 13). In this case, through the low-pass filter with a separation capacitor at the input, the signal V $\genfrac{}{}{0ex}{}{\text{-}}{\text{up}}$ (16, Fig. 13) is fed to the non-inverting input of the integrator I2 (Fig. 6) and, thereby, the signal from the output of the low-pass filter with the signals from the output of detector D5 (20, Fig. 13) and detector D6 (21 , Fig.13), which reduces the increment of the signal V _{and 2} from the output of the second PCF 10 at the time of a three-fold increase in phase shifts (2 and 3, Fig.13) in the absence of drift of the steepness of the modulators FM1 and FM2 and thereby the signal level from the main and additional outputs Converter FDA 11 (Fig.7) will be unchanged.

The signal V _{and 1} (22, Fig. 13) from the output of the integrator I1 of the first phase-sensitive rectifier ФЧВ9 (Fig. 6) is converted by the input switch 3K of the converter PCM 12 (Fig. 8), controlled by the signal of the IU with IP 13 (Fig. 10), into alternating the signal V _f1 (23, Fig.13). The sign of the signal V _{and 1} (22, Fig. 13) depends on the sign of speed, and the level - not only on the magnitude of the speed, but also on the speed-adjustable transmission coefficient of the integrator I3 (Fig. 9) in PKM12 (Fig. 8), which improves signal to noise ratio over a wide range of measured speed. Namely, the transfer coefficient of the I3 integrator is not only set at the command of the range switch (the resistor is short-circuited), but also decreases at the lower limit of the measured speed range (shunting of the resistor by diodes). The storage capacitor of the integrator I3 is short-term shunted by a key controlled by a pulse V _k4 to increase the speed of VOIUS when the speed sign changes. At the output of the integrator I3, a symmetric triangular waveform V and _{3 is} generated (24, Fig. 13), the amplitude of which is amplified by a thermocompensating amplifier UT to provide a phase difference Δφ _k = 2π rad at the moment of “resetting the saw” (signal Vп, 25, Fig. 13) generated by the 4KM converter PKM 12 switch (Fig. 8), controlled by the IU signal with IP 13 (Fig. 10), while the “tilt of the saw” (signal Vp, 25, Fig. 13) is determined by the speed value.

In the presence of a signal Vп (25, Fig. 13) at the main output of PCM12 (Fig. 8), counterpropagating emissions that have passed during the time of the IVK5 circuit have phase shifts at its outputs (26 and 27, Fig. 13) and after repeated modulation - phase shifts (28 and 29, Fig. 13).

The phase difference Δφ _to (30, Fig. 13) generated by the signal Vп (25, Fig. 13) supplied to the phase modulators from the main output of the PCM 12 (Fig. 8) has the form of a component equal to and sign opposite to the Sagnac phase, summed with a sequence of short-duration pulses of duration τ and amplitude 2π rad, with a frequency proportional to speed, and a sign coinciding with the sign of the Sagnac phase.

Channel stabilization scale factor works as follows. When the amplitude of the phase difference Δφ _in (1, Fig. 14) deviates from the calculated value, the total phase difference Δφ (2, Fig. 14) changes. With a three-fold increase in the amplitude Δφ _in (1, Fig. 14), the clock pulse F6 (3, Fig. 14), applied to one of the control inputs of the FDA converter 11 (Fig. 7), the radiation intensity increment has a component in the form of a sequence of short-time pulses, excellent from zero, with Δφ _c = Δφ _k (4, Fig. 14) and with Δφ _c ≠ Δφ _k (5, Fig. 14).

In this case, when converting the radiation intensity increment (4 and 5, Fig. 14) into an electric signal from the output of the converter unitary enterprise 8 (Fig. 4) controlled by the clock pulse F1 (6, Fig. 14), a signal is formed through a separation capacitor at Δφ _s = Δφ _to view (7, Fig. 14) and when Δφ _with ≠ Δφ _to view (8, Fig. 14), fed to the input of synchronous detectors D4 and D5 of the PCF rectifier 10 (Figure 6), controlled by the clock pulse F4 (9, Fig. 14) and F5 (10, Fig. 14). At the output of synchronous detectors D4 and D5, signals are generated at Δφ _c = Δφ _k (11 and 12, Fig. 14) and at Δφ _c ≠ Δφ _k signals (13 and 14, Fig. 14). The signal from the output of the low-pass filter at Δφ _c = Δφ _{to the} form (15, Fig. 14) and for Δφ _with ≠ Δφ _{to the} form (16, Fig. 14) is summed according to the differential circuit with signals of different levels from the output of the synchronous detectors D4 and D5 (11-14, Fig. 14). In both cases, the increment of the signal V ₂ (17, Fig. 14) from the output of the PCF 10 (Fig. 6), summed with the signal from the source of the IWP 14, changes the level of the reference voltage ± V _op and thereby changes the amplitude of the signal V _in from the output of the converter FDA 11 (Fig.7) and the signal V _p from the output of the converter PCM12 (Fig.8). In this case the calculated amplitude is set phase difference Δφ _in = π / 2 rad (1, 14) and _{to the} phase difference Δφ = Δφ _with rad when the saw reset, hence the sensitivity is stabilized, and continuous process formed the Sagnac phase compensation and thus improves interference immunity WOIUS. In addition, with a change in the level of the reference voltage ± _Vop , the pulse repetition rate from the VOIUS output changes (IP 13 output, Figure 10) and thereby, together with the UT amplifier of the PCM 12 converter (Figure 8), which compensates for the Sagnac phase drift, stabilization is ensured scale factor meter.

The formation of a sequence of pulses of a given duration, a frequency proportional to the speed, and also control signals supplied to the PCM converter 12 (Fig. 8) with the sign of the output speed of the pulse converter IP 13 (Fig. 10) is illustrated by the time diagram shown in Fig. 15 . At the same time, the converter’s self-tuning process is shown, namely, the state of the first D-trigger (1D frequency divider) and thereby the IP 13 output corresponds to the speed sign taking into account the state of the first RS-trigger (memory cell 1RS).

Let up to time t _{1 a} positive sign of speed corresponds to a positive signal level V _{and 1} (1, Fig. 15) from the output of the PCF 9 (Figure 5), while the output of the first D-trigger (1D, Figure 10) is the signal level L1 (2, Fig. 15) - LOG. 1, the signal level L1 ^- (3, Fig. 15) - LOG. 0. If the state of the first RS-trigger (1RS, Fig. 10) for the output α (4, Fig. 15) is LOG.0, for the output δ (5, Fig. 15) is LOG.1, then the signal level L2 ^is (6 , Fig.15) - LOG.1, the signal level L2 (7, Fig.15) - LOG.0. Therefore, the signal level of the DUT (8, Fig. 15) corresponds to the state of the output α (4, Fig. 15) - LOG.0, while the sign of the signal V _f1 (9, Fig. 15) at the inverting input of the integrator I3 of the PCM12 converter (Fig. .8) corresponds to the sign of the signal V _{and 1} (1, Fig. 15). The slope of the signal V and ₃ (10, Fig. 15) at the output of the integrator FROM is negative, which causes a high level (LOG.1) of the signal V _k2 (11, Fig. 15) to occur when the threshold for operation of the comparator K2 (Fig. 10) is reached.

In this case, the state at the output α (4, Fig. 15) is LOG.1, at the output δ (5, Fig. 15) is LOG.0, the signal level L2 ^is (6, Fig. 15) is LOG.0, the signal level of the DUT (8, Fig. 15) - LOG.1. The sign of the signal V _f1 (9, Fig. 15) is set opposite to the sign of the signal V _{and 1} (1, Fig. 15). The slope of the signal V and ₃ (10, Fig. 15) becomes positive, which causes, when the threshold for comparator K1 (Fig. 10) is reached, the appearance of a high level (LOG.1) of the signal V _k1 (12, Fig. 15). Again, the state of the first RS-trigger (1RS, Figure 10) for the output α (4, Figure 15) is LOG.0, for the output δ (5, Figure 15) is LOG.1, then the signal level L2 ^is (6 , Fig. 15) - LOG.1, and the signal level of the DUT (8, Fig. 15) - LOG.0. In this case, the phase of the DUT signal (8, Fig. 15) is determined by the initial state of the first RS-trigger (1RS, Fig. 10) and changes with a frequency determined by the slope of the signal V and ₃ (10, Fig. 15).

When LOG.1 appears at the output α (4, Fig. 15) or the output δ (5, Fig. 15), the high levels are formed at the outputs of the second or third D-flip-flops (pulse shapers of a given duration 2D and 3D, Fig. 10) signals L3 (13, Fig. 15) and L4 (15, Fig. 15), while the signal levels L3 ^- (14, Fig. 15) and L4 ^- (16, Fig. 15) - LOG.0 (for a short time). At the input and output of the fourth and fifth D-flip-flops (4D and 5D, Fig. 10), signals V and ₃ (10, Fig. 15) are formed, respectively, signals V _k3 (17, Fig. 15), V $\genfrac{}{}{0ex}{}{\text{-}}{\text{k3}}$ (18, Fig. 15) and L5 (19, Fig. 15), L5 ^- (20, Fig. 15).

At the output of the third RS-trigger (3RS, Figure 10), the signal level L6 (21, Figure 15) is LOG.1 from the moment of a high level (LOG.1) of signal L4 (15, Fig.15) and LOG.0 s a high level moment (LOG.1) of the L5 signal (19, Fig. 15). At the output of the second RS-trigger (2RS, Figure 10), the signal level L7 (22, Figure 15) is LOG.1 from the moment of a high level (LOG.1) of signal L3 (13, Figure 15) and LOG.0 s moment of a high level (LOG.1) of signal L5 ^- (20, Fig. 15). At a high level (LOG.1) of signals L5 ^- (20, Fig. 15) and L6 (21, Fig. 15), the signal level L8 (23, Fig. 15) at the output of the third AND-NOT cell (I3 ^- , Fig. 10) - LOG. 0. Similarly, with a high level of signals L5 (19, Fig. 15) and L7 (22, Fig. 15), the signal level L9 (24, Fig. 15) at the output of the fourth AND-NOT cell (I4 ^- , Fig. 10) is the LOG .0.

If the signal level L8 (23, Fig. 15) or L9 (24, Fig. 15) is LOG.0, then at the output of the second AND-NOT cell (I2 ^- , Fig. 10), signal L10 (25, Fig. 15) - LOG. 1. Similarly, if the signal level L3 ^- (14, Fig. 15) or L4 ^- (16, Fig. 15) - LOG.0, then at the output of the first cell AND-NOT (I1 ^- , Fig. 10), the signal L11 (26, Fig. 15) - LOG. 1. With a high signal level L10 (25, Fig. 15) or L11 (26, Fig. 15), the signal level L12 (27, Fig. 15) at the output of the second OR-NOT cell (2 OR ^- , Fig. 10) is LOG. 0. Moreover, if the signal level L1 ^- (3, Fig. 15) at the output of the first D-trigger (1D, Fig. 10) is LOG.0, then at the output of the third cell, OR-NOT (3 OR ^- , Fig. 10) - LOG. 1.

Thus, from one of the outputs of the converter IP 13 (Figure 10), corresponding to the positive sign of the signal V _{and 1} (1, Figure 15), when the comparators K1-K3 (Figure 10) are triggered, a sequence is formed (up to time t ₂ ) pulses (28, Fig. 15) with a frequency proportional to speed.

Suppose that at time t _{2 the} sign of the signal V _{and 1} (1, Fig. 15) will be reversed, therefore, the phase of the signal V _ф1 (9, Fig. 15) and the slope of the signal V and ₃ (10, Fig. 15) will change. However, when the signal V and ₃ reaches the comparator threshold (in our case, K1, Figure 10), the first RS-trigger (1RS, Figure 10) does not roll over with LOG 0 at the output α (4, Figure 15). In the presence of a high signal level V _k1 (12, Fig. 15), the signal V _k0 (30, Fig. 15) increases and when the threshold for comparator K4 (Fig. 10) is reached, the accumulative signal is shunted by the signal V _k4 (31, Fig. 15) capacitor in the feedback of the integrator I3. In this case, the signal V and ₃ (10, Fig. 15) decreases to zero, and at the output of the first D-flip-flop (1D, Fig. 10), a low level of signal L1 (2, Fig. 15) is set to LOG and a high level signal L1 ^- (3, Fig. 15) - LOG. 1. Considering that the state of the first RS-trigger (1RS, Fig. 10) for the output α (4, Fig. 15) is LOG.0, for the output δ (5, Fig. 15) is LOG.1, then the signal level L2 ^is (6, Fig. 15) and the signal level L2 (7, Fig. 15) - LOG.0.

With a low signal level L1 (2, Fig. 15), the signal level of the DUT (8, Fig. 15) corresponds to the state of the output δ (5, Fig. 15) - LOG.1, while the signal sign is V _f1 (9, Fig. 15) ) at the inverting input of the integrator I3 of the converter PCM12 (Fig. 8) opposite to the sign of the signal V _{and 1} (1, Fig. 15). The slope of the signal V and ₃ (10, Fig. 15) at the output of the integrator I3 is negative, which causes a high level (LOG.1) of the signal V _k2 (11, Fig. 5) to occur when the threshold for the operation of the comparator K2 (Fig. 10) is reached. In this case, the state at the output α (4, Fig. 15) is LOG.1, at the output δ (5, Fig. 15) is LOG.0, the signal level L2 (7, Fig. 15) is LOG.1, level signal DUT (8, Fig.15) - LOG. 0. The sign of the signal V _f1 (9, Fig. 15) corresponds to the sign of the signal V _{and 1} (1, Fig. 15). The slope of the signal V and ₃ (10, Fig. 15) becomes positive, which causes, when the threshold for comparator K1 (Fig. 10) is reached, the appearance of a high level (LOG.1) of the signal V _k1 (12, Fig. 15). In this case, the state of the first RS-trigger (1RS, Figure 10) for the output α (4, Figure 15) is LOG.0, for the output δ (5, Figure 15) is LOG.1, then the signal level is L2 ( 7, Fig. 15) is LOG. 0, and the signal level of the DUT (8, Fig. 15) is LOG. 1.

Thus, with a negative sign of speed, the signal level L1 (2, Fig. 15) at the output of the first D-trigger (1D, Fig. 10) is LOG.0, the signal level of the DUT (8, Fig. 15) corresponds to the signal level at the output δ (5, Fig. 15) of the first RS-trigger (1RS, Fig. 10) and when the comparators K1-K3 (Fig. 10) are triggered, it is similar to the positive sign of the speed at the output of the fourth cell OR-NOT (4 OR ^- , Fig. 10 ) a sequence of pulses is formed with a frequency proportional to speed.

Claims (6)

1. Fiber-optic angular velocity meter containing a measuring fiber circuit made of a single-core anisotropic single-mode fiber with preserving polarization in the form of a coil with symmetrical winding relative to the middle of the total length, a radiation source made in the form of a broadband superluminescent diode, a trip-connection device, two photodetector modules, depolarizer, phase modulators of auxiliary and compensating modulation, signal conversion and isolation device, incl a multi-channel synchronizing pulse generator, a first phase-sensitive rectifier with two control inputs, a pulse converter, one of the outputs of which is the output of the meter, and a secondary power source, while the first phase-sensitive rectifier is made according to the double synchronous detection scheme in the form of a summing integrator, to the inputs of which are connected two synchronous detectors, the control inputs of which are connected to the outputs of the generator of synchronizing pulses, and the clock pulses at the control inputs of the first phase-sensitive rectifier have a duration of less than half a period and are shifted relative to each other by an odd number of half periods of the auxiliary modulation frequency, characterized in that a thermistor and a microcooler are inserted, integrated with a photo diode of the second photodetector module into the radiation source, a thermal control amplifier, made in the form series-connected bridge amplifier, with a thermistor in feedback, and a power amplifier output connected to a microcooler, a splitting-connection device is made in the form of a serially optically coupled input splitter, a polarizer and a contour splitter, the output arms of which include broadband phase modulators optically coupled to the measuring fiber circuit, the first output of the radiation source is optically coupled through the depolarizer to the input of the input splitter, the first the output of which is optically coupled to the waveguide polarizer, the second output of the input splitter is optically coupled through a length of a homode fiber with a photodiode of the first photodetector module with a differential output and with isolation capacitors at the differential inputs, the second output of the radiation source is optically coupled through a photodiode of the second photodetector module with its input, and a rectangular voltage amplifier with a differential output is additionally introduced into the signal conversion and isolation device made according to the scheme of double synchronous detection with one control input in the form of series-connected through synchronous detectors of two differential amplifiers with isolation capacitors at the differential inputs, a second phase-sensitive rectifier with two control inputs, an input through the isolation capacitor connected to one of the differential outputs of the rectangular voltage amplifier-converter, the auxiliary voltage phase-modulation rectangular voltage converter with two control inputs, the main input connected to the output of the second phase-sensitive rectifier and will complement an input input with an output of a secondary power source, a sawtooth voltage converter of compensating phase modulation with two control inputs and, through a first phase-sensitive rectifier with isolation capacitors at the input, connected to the output of a rectangular voltage amplifier-converter, while the auxiliary output of the rectangular voltage converter phase modulation connected to the main output of the sawtooth voltage converter comp nasal phase modulation through a parallel connected push-pull circuit broadband phase modulators auxiliary and compensating modulation, the additional outputs of the rectangular voltage converter auxiliary phase modulation connected to the symmetrical reference inputs of the pulse Converter, an additional reference input connected to the output of the secondary power source and the main input connected to the additional output of the converter sawtooth voltage compensating phases modulation, the control inputs connected to two additional outputs of the pulse converter, the outputs of the multichannel synchronization pulse shaper are connected to the control inputs of the synchronous detectors of the rectangular voltage amplifier-converter and the second phase-sensitive rectifier, as well as to the control inputs of the serial-parallel switches of the rectangular voltage converter of the auxiliary phase modulation and control circuits of the secondary power source, with e The clock pulse at the control input of the rectangular-voltage amplifier-converter has a duration shorter than the time it takes to light the measuring fiber circuit with a repetition interval equal to the shift of the clock pulses at the control inputs of synchronous phase-sensitive rectifier detectors and half the clock pulse at one of the control inputs of the square-wave converter of auxiliary phase modulation with an interval sequence equal to the interval of the synchronization pulses on the control second inputs constituent phase-sensitive rectifier, the synchronous clock type "meander" duty cycle two at the second control input of the auxiliary converter rectangular voltage phase modulation has a repetition interval equal to the period of the auxiliary frequency phase modulation, a multiple of the interval following the sync control input of phase-sensitive rectifiers. 2. The fiber-optic angular velocity meter according to claim 1, characterized in that the splitting-connection device is made in the form of an input splitter and an optical integrated circuit containing a waveguide polarizer and a Y-shaped waveguide distributor. 3. The fiber-optic angular velocity meter according to claim 1, characterized in that the second phase-sensitive rectifier is made according to a double synchronous detection scheme in the form of an integrating adder-subtractor connected to the rectifier input with an inverting input through two parallel-connected synchronous detectors and a non-inverting input through a passive filter, while the output of the adder-subtractor is the output of the rectifier. 4. The fiber-optic angular velocity meter according to claim 1, characterized in that the auxiliary phase modulation rectangular voltage converter comprises a chain of series-connected summing amplifier, the inputs of which are the inputs of the converter, and an inverter, the outputs of which are additional outputs of the converter and connected to the inputs two series-parallel switches with voltage dividers on one of the inputs, while the outputs of the switches, the control input of which is th inverter control input connected to the inputs of the third series-parallel switch, the control input of which is the second control input of the inverter, and the output is the main output of the converter. 5. The fiber-optic angular velocity meter according to claim 1, characterized in that the sawtooth voltage converter for compensating phase modulation contains an integrator with variable slope, one of the input resistors of which is shunted by diodes, and an integrating capacitor, shunt key, the control input of which is one of the control inputs of the converter, while the input resistors through the input serial-parallel switch with an inverter at one of the inputs are connected to the input of the converter, the additional output of which is the output of the integrator, and the main output is the output of an additional serial-parallel switch with an inverter at one of the inputs connected via a temperature compensating link to the output of the integrator, while the control input of the switches is the second control input of the converter. 6. The fiber-optic angular velocity meter according to claim 1, characterized in that the pulse converter is made in the form of a unified self-adjusting device containing comparators, RS-triggers, D-triggers and two-input logic elements OR-NOT, AND-NOT, while the first RS-trigger with inputs connected to the outputs of the first and second comparators, the first inputs of which are connected to the first input of the third comparator and are the main input of the converter, the first input of the fourth comparator is connected via RC-chains with outputs the first and second comparators, the second inputs of which are symmetric reference inputs of the converter, the second input of the third comparator is connected to a common bus, and the second input of the fourth comparator is an additional reference input of the converter, one of the additional outputs of which is the output of the fourth comparator connected to the clock input of the first D -trigger, the second RS-trigger with inputs connected to the main outputs of the second and fifth D-triggers, the third RS-trigger with inputs connected to the main outputs of the third the fourth D-flip-flops, while the clock inputs of the second and third D-flip-flops are connected to the outputs of the first RS-flip-flop, the clock input of the fourth D-flip-flop is connected to the output of the third comparator, connected to the clock input of the fifth D-flip-flops through the first OR element -NOTE, the inverse outputs of the second and third D-flip-flops are connected to the inputs of the first AND-NOT element, the output connected to one of the inputs of the second OR-NOT element, the second input connected to the output of the second AND-NOT element, the inputs connected to the output the third and fourth AND-NOT elements, while the inputs of the third AND-NOT element are connected to one of the outputs of the third RS-trigger and to the main output of the fifth D-trigger, and the inputs of the fourth AND-NOT element are connected to one of the outputs of the second RS-trigger and to the main output of the fourth D-trigger, the output of the second OR-NOT element is connected to one of the inputs of the third and fourth OR-NOT elements, the outputs of which are the output of the converter, and the second inputs are connected to the outputs of the first D-trigger connected to one of the inputs fifth and sixth elemen OR-NOT, the second inputs are connected to the outputs of the first RS-trigger, and the outputs are to the inputs of the seventh OR-NOT element, the output of which is the second additional output of the converter, while the first and third RS-triggers are made of two OR-NOT elements, the first inputs of which are covered by cross-links, and the second inputs are inputs of RS-flip-flops, the second RS-flip-flop is made of D-flip-flop, controlling inputs connected to a common bus.

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