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EP2425680B1 - Circuit pour faire fonctionner des diodes luminescentes - Google Patents

Circuit pour faire fonctionner des diodes luminescentes Download PDF

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Publication number
EP2425680B1
EP2425680B1 EP10721272.2A EP10721272A EP2425680B1 EP 2425680 B1 EP2425680 B1 EP 2425680B1 EP 10721272 A EP10721272 A EP 10721272A EP 2425680 B1 EP2425680 B1 EP 2425680B1
Authority
EP
European Patent Office
Prior art keywords
current
led
switch
secondary winding
operating circuit
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Not-in-force
Application number
EP10721272.2A
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German (de)
English (en)
Other versions
EP2425680A2 (fr
Inventor
Stefan Zudrell-Koch
Michael Zimmermann
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Tridonic GmbH and Co KG
Original Assignee
Tridonic GmbH and Co KG
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Publication of EP2425680A2 publication Critical patent/EP2425680A2/fr
Application granted granted Critical
Publication of EP2425680B1 publication Critical patent/EP2425680B1/fr
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Classifications

    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/10—Controlling the intensity of the light
    • H05B45/14—Controlling the intensity of the light using electrical feedback from LEDs or from LED modules
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/32—Pulse-control circuits
    • H05B45/327—Burst dimming
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/37—Converter circuits
    • H05B45/3725—Switched mode power supply [SMPS]

Definitions

  • the invention relates to an operating circuit with light emitting diodes according to the preamble of patent claim 1 and a method for operating light emitting diodes according to the preamble of patent claim 12.
  • LEDs have become an attractive alternative to conventional light sources such as incandescent or gas discharge lamps.
  • LED light-emitting diode
  • This term is intended below to include both light emitting diodes of inorganic materials as well as light emitting diodes of organic materials. It is known that the light emission of LEDs correlates with the current flow through the LEDs. For brightness control, LEDs are therefore always operated in a mode in which the current flow through the LED is controlled.
  • switching regulators for example step-down or buck converters, are preferably used to drive an arrangement of one or more LEDs.
  • a switching regulator is for example from the DE 14 2006 034 371 A1 known.
  • a control unit controls a high-frequency clocked switch (for example, a power transistor). When the switch is turned on, current flows through the LED assembly and a coil, which is charged by it. The cached energy of the coil discharges in the off state of the switch via the LEDs (freewheeling phase).
  • the current through the LED arrangement shows a zigzag time course: when the switch is on, the LED current shows a rising edge, with the switch off, there is a falling edge.
  • the time average of the LED current represents the RMS current through the LED array and is a measure of the brightness of the LEDs. By appropriate timing of the circuit breaker, the average, effective current can be controlled.
  • the function of the operating device is now to set a desired average current flow through the LEDs and to minimize the temporal fluctuation of the current due to the high frequency switching on and off of the switch (typically in the range above 10 kHz).
  • a large fluctuation range of the current has a disadvantageous effect particularly with LEDs, since the spectrum of the emitted light can change as the current amplitude changes.
  • the LEDs are supplied by the operating device low-frequency (typically with a frequency in the range of 100-1000 Hz) PWM packets with (in the time average) constant current amplitude.
  • the current within a PWM packet is superimposed on the high-frequency ripple listed above.
  • the brightness of the LEDs can now be controlled by the frequency of the PWM packets; For example, the LEDs can be dimmed by increasing the time interval between the PWM packets.
  • a practical requirement for the operating device is that it can be used as flexibly and versatile as possible, for example independently how many LEDs are actually connected and operated as a load.
  • the load may also change during operation if, for example, an LED fails.
  • FIG. 1a As shown in the example shown, a buck converter for the operation of at least one LED (or several LEDs connected in series), which has a switch S1, is shown as a basic circuit.
  • the operating circuit is supplied with a DC voltage or a rectified AC voltage U0.
  • the known circuits require complex measuring circuits in order to measure the current through the LED during the switch-off phase, for example, this can be done by a voltage measurement across the LED, from which the current is concluded. But a differential voltage measurement at high potential is necessary.
  • the EP0948241 shows an operating circuit for an LED, which is formed by a buck converter.
  • a coil N1 magnetized by closing a series-connected switch K1, while with open switch K1, the coil N1 is demagnetized via a freewheeling path D1, K2.
  • the buck converter is operated in a so-called limit operation. Once the coil N1 is demagnetized, the switch K1 is turned on again.
  • the detection of the demagnetization of the coil N1 by means of a secondary winding N2 coupled thereto. As long as the coil N1 is still magnetized during the freewheeling phase, a voltage drops over it. This voltage is almost constant as long as there is magnetization of the coil N1. Only at the moment when the coil N1 is demagnetized does the voltage across the coil N1 collapse. By monitoring the voltage at the secondary winding N2 can thus be easily detected, for example by means of a comparator, the time of demagnetization.
  • the operating circuit is supplied with a DC voltage or rectified AC voltage for at least one LED.
  • a supply voltage for at least one LED is provided by means of a coil and a switch clocked by a control / regulating unit, wherein when the switch in the coil, an energy is stored, which discharges when the switch is switched off via a diode and at least one LED.
  • control unit selects the switch-on time and the switch-off time of the switch so that the current flow through the at least one LED has the smallest possible ripple.
  • the operating circuit drives at least one LED, which is supplied with a DC voltage or rectified AC voltage, and which provides a supply voltage for at least one LED by means of a coil and a switch clocked by a control unit, wherein when the switch is switched on in the coil, an energy is temporarily stored itself with the switch off via at least one LED discharges, wherein in series with the LED, a transformer having a primary winding and a secondary winding is arranged, and a measuring element is arranged in series with the secondary winding, so that a secondary circuit is formed, wherein in the secondary winding defined current is fed and at least one measurement takes place on the secondary side.
  • the time is detected at which the fed defined current reaches a value that the transformer is no longer due to the LED current (iLED) on the primary side in saturation.
  • the invention basically allows the use of two magnetically coupled windings as a coupled energy storage for measuring a current through an LED, wherein this measurement can be carried out electrically isolated.
  • a method for operating at least one LED allows, wherein a supply voltage for the LED is provided by means of a coil and a clocked switch, wherein the switch is in the coil, an energy buffered, which discharges when the switch is off via the LED, wherein a secondary winding a transformer whose primary winding is arranged in series with the LED, a defined current is fed and at least a measurement is made on the secondary side to determine the time for turning on the switch, characterized in that the time for switching on the switch is detected, when the fed defined current reaches a value that the transformer is no longer due to the LED current is in saturation on the primary side.
  • the operating circuit comprises a sensor unit which generates a sensor signal and monitors the current through the LED.
  • control unit uses a signal of the sensor unit or a combination with the signal of an optional further sensor unit for determining the switch-on and switch-off of the switch.
  • control unit turns off the switch when the current through the LED exceeds a maximum reference value, and turns on again at the time when the current through the LED falls below a minimum reference value.
  • the sensor unit is formed by two magnetically coupled windings, for example by the windings of a transformer.
  • the operating circuit has a capacitor arranged in parallel with the at least one LED, which maintains the current through the LED during the demagnetization phase of the coil, so that the current through the LEDs is smoothed.
  • FIG. 1 a and FIG. 1b show the state of the art.
  • circuitry is used to operate at least one (or more series-connected) LED.
  • one LED or more series-connected LEDs.
  • two LEDs are connected in series, it can of course be only one or more LEDs.
  • the LED or the serially switched LEDs are collectively referred to below as the LED (or LED strip called).
  • An advantage of the present invention is that the operating circuit adapts very flexibly to the type and number of serially connected LEDs.
  • the circuit is supplied with a DC voltage U0, which of course can also be a rectified AC voltage.
  • the LEDs are connected in series with a coil L1 and a switch S1.
  • the circuit arrangement has a diode D1 (the diode D1 and the coil L1 are connected in parallel with the LEDs) and optionally a capacitor C1 connected in parallel with the LEDs. In the switched-on state of the switch S1, current flows through the LEDs and through the coil L1, which is thereby magnetized.
  • the stored energy in the magnetic field of the coil discharges in the form of a current through the diode D1 and the LEDs.
  • the capacitor C1 is charged.
  • the capacitor C1 discharges and contributes to the flow of current through the LED track. With suitable dimensioning of the optional capacitor C1, this can lead to a smoothing of the current through the LEDs.
  • the coil L1 may also be part of a power transmitting transformer.
  • switch S1 a field effect transistor is preferably used.
  • the switch S1 is switched to high frequency, typically in a frequency range of over 10 kHz.
  • the current can be measured by the LED and thus kept at a predetermined value or in a predetermined value range.
  • Another advantage of the invention is that the switch S1 can be spared in operation because, as explained later, it can be switched on when the power applied to it is almost zero.
  • control and / or regulating unit SR (hereinafter also referred to as control / regulating unit SR) is provided, which specifies the timing of the switch S1 for controlling the LED power or the LED current iLED.
  • the control / regulation unit SR uses as input variables signals from an optional further sensor unit SE1 and at least signals from a sensor unit SE2 to determine the exact switch-on and -off timing of the switch S1. Since the sensor unit SE2 is located in the path where a measurement on the LED is possible during the turn-off phase of the switch S1, this sensor unit is referred to below as the sensor unit SE2.
  • the only optional further sensor unit SE1 allows only one measurement during the switch-on of the switch S1 and is therefore referred to as the further sensor unit SE1.
  • the sensor unit SE2 is arranged within the current branch, which is traversed by the current during the freewheeling phase, preferably in series with the LED or alternatively also in series with the coil L1 (designated as SE2 ').
  • the control unit / control unit SR can set a suitable time for the switch-on time of the switch S1 and optionally also the suitable time for the switch-off time of the switch S1.
  • the switch S1 is turned off when the current through the LED is below a certain value, and the switch S1 is turned on when the current through the LED exceeds a certain value.
  • the switch S1 can be switched on even if the current through the coil L1, immediately after the diode D1 locks in the freewheeling phase, is zero for the first time or at least very low. Then, at the switch-on time of the switch S1, the lowest possible current is applied to the switch S1. By detecting the current zero crossing through the coil, a nearly lossless switching is possible.
  • the current through the LEDs shows only slight ripple and does not vary greatly. This is due to the application of the method according to the invention for measuring the LED current iLED and, if the capacitor C1 is present, also due to the smoothing effect of the capacitor C1 connected in parallel with the LEDs.
  • switch S1 is closed and current begins to flow through the LED and coil L1.
  • the current i_L shows an increase according to an exponential function, wherein in the range of interest here a quasi-linear increase of the current iLED and i_L takes place.
  • iLED differs from i_L in that part of the current i_L contributes to the charge of the capacitor C1.
  • the opening of the switch S1 at time t_1 (for example, when a desired maximum reference value is reached) has the consequence that the energy stored in the magnetic field of the coil L1 is discharged via the diode D1 and the LEDs or the capacitor C1.
  • the current i_L continues to flow in the same direction, but decreases continuously and can even reach a negative value.
  • the switch S1 is already switched on again when the current iLED has fallen below a desired minimum reference value by the LED, this desired minimum reference value according to a preferred embodiment being only slightly below the desired maximum reference value (which determines the switching off of the switch S1 ) in order to achieve as constant a current iLED as possible through the LED.
  • a negative current (ie reverse current flow) can be achieved when the coil L1 is demagnetized. This is present as long as the charge carriers, which were previously enriched in the conducting-poled diode D1, are eliminated from the barrier layer of the diode D1.
  • the current iLED decreases only weakly and is maintained because the capacitor C1 has a smoothing effect.
  • the diode blocks.
  • the current i_L decreases (but is still negative) and goes to zero. In this phase, parasitic capacitances at the diode D1 and other parasitic capacitances in the remaining circuit are charged.
  • An advantageous switch-on time t_3 for the switch S1 can now also be given if the current i_L reaches the zero crossing, or at least the vicinity of the zero crossing. At this time, the coil L1 is not or hardly magnetized. The switch S1 can be turned on at this time with very low losses, since hardly any current flows through the coil L1.
  • the sensor unit SE2 For detecting the advantageous switch-on time for switch S1, the sensor unit SE2 is now used.
  • the current i_L can be detected by the LED by means of the transformer, as also described in the following with reference to FIG Fig. 3a and 3b is described.
  • the current iLED through the LED or alternatively the current i_L through the coil L1 can also be detected, for example, by means of a Hall sensor.
  • the sensor unit SE2 is a series to the LED-connected transformer with a primary winding T1) and a secondary winding T2.
  • a measuring element RM is arranged in series with the secondary winding T2, so that a secondary circuit is formed, wherein in the secondary winding T2, a defined current is fed and at least one measurement takes place on the secondary side.
  • the monitoring of the temporal voltage curve on the secondary side T2 allows a statement about the advantageous reconnection time of the switch S1.
  • the switch S1 it is also possible for the switch S1 to be controlled by the control / regulating unit SR in such a way that the mean value of the current iLED is regulated by the LED.
  • the control unit SR can control the switch S1 such that the LED current iLED is regulated to a predetermined value.
  • the optional further sensor unit SE1 is arranged in series with the switch S1 and detects the current flow through the switch S1. This serves to monitor the flow of current through the switch S1. If the current flow through the switch S1 exceeds a certain maximum reference value, the switch S1 is turned off.
  • the further sensor unit SE1 can be, for example, a measuring resistor (shunt), as described later as a measuring resistor RS in the examples of FIG FIGS. 3 to 5 is shown.
  • the voltage drop at the measuring resistor (shunt) RS can now be tapped and, for example, compared with a reference value by means of a comparator. If the voltage drop at the measuring resistor (shunt) RS exceeds a certain value, the switch S1 is switched off.
  • the monitoring by means of the optional further sensor unit SE1 can be used at least in addition or alternatively to the sensor unit SE2 for the detection of the switch-off condition of the switch S1. Above all, it can also be used to protect the switch S1 against overcurrents in the event of a fault.
  • the control unit SR uses the information from the optional further sensor unit SE1 and the sensor unit SE2 to determine the on and off timing of the switch S1.
  • the regulation of the (time-averaged) LED power by the control unit / regulation unit SR for adjusting the brightness of the LED can be carried out, for example, in the form of PWM packets.
  • the frequency of the PWM packets is typically of the order of 100-1000 Hz. However, the switch S 1 itself is turned on and off during the PWM packets at a much higher frequency.
  • FIG. 3 A possible embodiment of the invention is in the Fig. 3 ( 3a and 3b ).
  • an operating circuit for at least one LED is shown, to which a DC voltage or rectified AC voltage is supplied, and which provides a supply voltage for at least one LED by means of a coil L1 and a clocked by a control / regulating unit SR switch S1.
  • a control / regulating unit SR switch S1 When the switch S1 is energized in the coil L1, an energy is stored, which discharges when switched off switch S1 via at least one LED.
  • the operating circuit may be controlled so that the control unit SR determines the time toff between a turn-off and a subsequent turn-on of the switch S1 depending on the measurement of the current iLED by the LED.
  • control / regulation unit SR can determine the current through the LED by means of a series-connected to the LED transformer with a primary winding T1 and a secondary winding T2.
  • control / SR unit feed an increasing current in the secondary winding T2 of the transformer. This is preferably done by a current source loff arranged in the control / regulation unit SR.
  • the control unit SR can monitor the voltage across the secondary winding T2 of the transformer via an analog-to-digital converter ADC.
  • ADC analog-to-digital converter
  • the defined current which is fed into the secondary winding T2 by the current source loff, may be a triangular current.
  • the defined current which is fed into the secondary winding T2 by the current source loff can also be a triangular current with a fixed DC component DC offset.
  • the defined current which is fed into the secondary winding T2 by the current source loff can also be, for example, a DC reference current with a fixed amplitude, to which an AC voltage component with a defined amplitude and frequency is superimposed.
  • the defined current may have a different stability, this may in particular be the case when saturation in the secondary winding T2 is reached.
  • different signal forms may be advantageous for the defined current, and the method for evaluating the measurement on the secondary side may be adapted to the type of current source loff used.
  • a current measurement is made possible by the very accurate monitoring of a current can be determined, wherein the current can also be a direct current.
  • this current measurement can be carried out such that a potential separation between the current path to be measured and the measuring evaluation circuit (T2 and SR) is given.
  • the current to be measured (which as already mentioned may also be a direct current) has an amplitude which is above the saturation current of the transformer, preferably the current to be measured is significantly above the saturation current of the transformer in order to ensure reliable measurement.
  • the transformer is operated in saturation when the current to be measured with a corresponding amplitude through the transformer (ie, through the primary winding T1) flows.
  • the secondary winding T2 saturates, which can be recognized by a secondary-side monitoring (for example via the measurement at the resistor RM).
  • a secondary-side monitoring for example via the measurement at the resistor RM.
  • the primary winding T1 forms a first energy storage element, wherein a current flows through the LED and through the primary winding T1 as a first energy storage element, wherein the primary winding T1 is coupled as a first energy storage element to the secondary winding T2 as a second energy storage element.
  • a defined current is fed with preferably increasing amplitude, so the time be recognized, to which the first Energy storage element due to the current through the second energy storage element again achieved an energy storage capability, ie the primary winding T1 leaves the state of saturation.
  • a control unit SR can monitor the voltage across the secondary winding T2 via an analog-to-digital converter ADC, for example at the measuring point C3 on the resistor RM.
  • an analog-to-digital converter ADC instead of an analog-to-digital converter ADC, however, the measurement can also take place, for example, by means of a comparator. For example, once the monitored voltage exceeds a reference voltage supplied to the comparator, it may be determined that the transformer is no longer in saturation due to the LED current on the primary side.
  • control unit SR is designed so that it can both supply a current through the same connection (by means of the integrated current source loff and at the same time can monitor the voltage at the terminal C2 (by means of an analogue-to-digital converter ADC) in order to use it perform the measurement on the secondary winding T2.
  • control unit SR is designed such that it can feed a current into the secondary winding T2 via a first terminal C2 (by means of the integrated current source loff) and can monitor the voltage across the resistor RM by means of the terminal C3 (by means of an analog-digital Converter ADC) to perform the measurement on the secondary winding T2.
  • a plurality of measured values within a predetermined time interval can also be detected and evaluated together.
  • the voltage across the resistor RM can be detected at the time when it is determined that the transformer is no longer due to the LED current on the primary side is in saturation or is again in saturation.
  • the maximum peak value of the voltage across the resistor RM which is reached when the current fed into the secondary winding T2 reaches its maximum value, can also be detected.
  • the monitoring at the terminal C2 can also be done by means of a comparator.
  • a comparator can preferably also be provided for the evaluation, which constantly toggles (ie in particular switches the reference) to both Flanks of the defined Electricity for monitoring. For example, different references for the rising and falling edge may be provided.
  • the signal can also be monitored and evaluated over time.
  • the time duration can be monitored until it is determined that the transformer is no longer in saturation due to the LED current on the primary side.
  • the reference of the comparator can for example also be specified by a digital-to-analog converter.
  • the control unit SR can perform the measurement of the current such that the defined current is fed to the secondary winding T2 by the current source loff only during the switch-off phase of the switch S1.
  • the control unit SR may perform the measurement of the current iLED by the LED (by means of the voltage across secondary winding T2) during the turn-off phase.
  • the current can be measured by the LED by means of a sensor unit SE2 by means of a transformer.
  • the sensor unit SE2 can also be a Hall sensor, in particular be formed by mutually coupled elements of a Hall sensor.
  • FIGS. 4 and FIG. 5 show specific embodiments of the invention.
  • FIG. 4 shows a modification of the circuit in FIG. 3 in that in addition a second switch S2 is arranged in parallel with the LEDs and the capacitor C1.
  • the switch S2 is selectively / independently controllable and may for example be a transistor. If the switch S2 is closed, the discharge process of the capacitor C1 is accelerated. The accelerated discharge of the capacitor C1 is achieved; that the current flow through the LED goes as fast as possible to zero.
  • the switch S2 can be activated and driven at a low dimming level, where the PWM packets are very short and it is important that the current through the LED rapidly approaches zero at the end of a PWM packet.
  • a low dimming level can be achieved by suitable control of the switch S2.
  • switch S2 Another function of this switch S2 is that it bridges the LEDs when switched on. This is required, for example, when the LEDs are to be turned off, i. should not emit light, but the supply voltage U0 is still present. Without bridging by switch S2, a (smaller) current would flow across the LEDs and resistors R1 and R2, and the LEDs would (slightly) light up.
  • the method of measuring the current through the LED preferably for detecting an advantageous on-time and / or off-time for the switch S1
  • FIG. 5 shows a modification of the circuit of FIG. 2a in that the arrangement of the inductor L1, the diode D1 and the orientation of the LED track is modified.
  • the circuit shown represents a so-called.
  • Buck-boost converter also referred to as inverter circuit
  • inverter circuit in series with the LED turn a transformer with a primary winding T1 and a secondary winding T2 is arranged.
  • a measuring element RM is arranged in series with the secondary winding T2, so that a secondary circuit is formed, wherein in the secondary winding T2, a defined current is fed and at least one measurement takes place on the secondary side for monitoring the LED current iLED.
  • Fig. 6 shows a section of an operating circuit for at least one LED analogous to the circuits of the previous examples.
  • Such an operating circuit typically drives at least one LED to which a DC voltage or rectified AC voltage is applied, and which provides a supply voltage for at least one LED by means of a coil L1 and a switch S1 clocked by a control unit SR, with switch S1 in the Coil L1 is cached an energy that discharges when switched off switch S1 via at least one LED, wherein in series with the LED, a transformer having a primary winding T1 and a secondary winding T2 is arranged, and a measuring element RM is arranged in series with the secondary winding T2, so that a secondary circuit is formed, wherein in the secondary winding T2, a defined current is fed and at least one measurement takes place on the secondary side.
  • the defined current IM is fed to the secondary winding T2 through a current source loff, which is connected to the secondary winding T2.
  • the measuring element may be a resistor RM (eg a current measuring shunt).
  • the current iLED on the secondary side can be determined by the LED.
  • the defined current IM which is fed to the secondary winding T2 as the coupled winding, may be a triangular current.
  • the time can be detected when the injected triangular current exceeds the current iLED through the LED.
  • This time can be detected by a voltage monitoring or measurement on the secondary winding T2 as a coupled winding.
  • the winding ratio of the transformer can be taken into account when determining the current.
  • the winding ratio of the transformer is one to one (1: 1).
  • the transformer may form the sensor unit SE2.
  • the sensor unit SE2 can also be a Hall sensor, in particular the sensor unit SE2 can be formed by elements of a Hall sensor which are coupled to one another.
  • a capacitor C1 may be disposed in parallel with the at least one LED, and maintains the current iLED through the LED during the phase of demagnetization of the coil L1, so that the current iLED is smoothed by the LEDs.
  • a switch S2 may be arranged in parallel to the capacitor C1 and the LEDs and be independently controllable.
  • the switch S2 can be closed to accelerate the discharging operation of the capacitor C1.
  • a control unit SR can monitor the voltage across the secondary winding T2 via an analog-to-digital converter ADC.
  • a method for operating at least one LED is made possible by means of a switching regulator circuit to which a DC voltage or rectified AC voltage is supplied and which provides a supply voltage for at least one LED by means of a coil L1 and a switch S1 clocked by a control unit SR switched on switch S1 in the coil L1, an energy is stored, which discharges when switch S1 is switched off via a diode D1 and at least one LED, and the current iLED flows through the LED through a first energy storage element which is coupled to a second energy storage element, and the first energy storage element due to the current iLED through the LED reaches its maximum energy storage capacity at least, wherein in the second energy storage element, a defined current IM preferably is increased in amplitude, so that the time can be detected at which the first energy storage element due to the current through the second energy storage element again obtains an energy storage capability.
  • the defined current IM which is fed into the second energy storage element, can also have a triangular shape.
  • the mutually coupled energy storage elements thus form the sensor unit SE2 and can be formed by magnetically coupled windings of a transformer T1, T2.
  • the coupled energy storage elements that form the sensor unit SE2 can also be formed by mutually coupled elements of a Hall sensor.
  • the switching regulator circuit forms an operating circuit for at least one LED.

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  • Circuit Arrangement For Electric Light Sources In General (AREA)
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  • Measurement Of Current Or Voltage (AREA)

Claims (12)

  1. Circuit d'attaque destiné à au moins une LED (diode électroluminescente) qui est alimentée par une tension continue ou une tension alternative redressée et qui fournit une tension d'alimentation destinée à la LED au moyen d'une bobine (L1) et d'un commutateur (S1) cadencé par une unité de commande/régulation (SR), dans lequel, lors de la fermeture du commutateur (S1), la bobine (L1) stocke temporairement une énergie qui se décharge à travers la LED lors de l'ouverture du commutateur (S1), dans lequel un transformateur comportant un enroulement primaire (T1) et un enroulement secondaire (T2) est disposé en série par rapport à la LED, et un élément de mesure (RM) est disposé en série par rapport à l'enroulement secondaire (T2), caractérisé en ce qu'un courant défini est injecté dans l'enroulement secondaire (T2) et au moins une mesure est effectuée du côté du secondaire, dans lequel on détecte l'instant où le courant défini injecté atteint une valeur telle que le transformateur n'est plus à saturation du côté du primaire en raison du courant de LED (iLED).
  2. Circuit d'attaque selon la revendication 1, caractérisé en ce que le courant (iLED) passant à travers la LED peut être déterminé au moyen de la mesure effectuée du côté du secondaire.
  3. Circuit d'attaque selon la revendication 1 ou 2, caractérisé en ce que le courant défini qui est injecté dans l'enroulement secondaire (T2) est un courant en dents de scie.
  4. Circuit d'attaque selon l'une quelconque des revendications 1 à 3, caractérisé en ce que l'instant est détecté par une surveillance de la tension ou une mesure effectuée sur l'enroulement secondaire (T2).
  5. Circuit d'attaque selon l'une quelconque des revendications précédentes, caractérisé en ce que le transformateur forme une unité de détection (SE2).
  6. Circuit d'attaque selon l'une quelconque des revendications précédentes, caractérisé en ce que l'enroulement secondaire (T2) est alimenté avec le courant défini au moyen d'une source de courant (Ioff).
  7. Circuit d'attaque selon l'une quelconque des revendications précédentes, comprenant un condensateur (C1) qui est disposé en parallèle par rapport à l'au moins une LED et qui maintient le courant passant à travers la LED pendant la phase de démagnétisation de la bobine (L1) de manière à lisser le courant (iLED) passant à travers les LED.
  8. Circuit d'attaque selon l'une quelconque des revendications précédentes, dans lequel l'unité de commande/régulation (SR) commande le commutateur (S1) de telle manière que le courant de LED (iLED) soit réglé à une valeur prédéterminée.
  9. Circuit d'attaque selon l'une quelconque des revendications précédentes, caractérisé par un commutateur supplémentaire (S2) qui est disposé en parallèle par rapport au condensateur (C1) et aux LED et qui peut être commandé indépendamment.
  10. Circuit d'attaque selon la revendication 9, caractérisé en ce que le commutateur (S2) est fermé afin d'accélérer le processus de décharge du condensateur (C1).
  11. Circuit d'attaque selon l'une quelconque des revendications précédentes, caractérisé en ce que l'unité de commande/régulation (SR) surveille la tension aux bornes de l'enroulement secondaire (T2) au moyen d'un convertisseur analogique-numérique (ADC).
  12. Procédé d'attaque d'au moins une LED, dans lequel une tension d'alimentation destinée à la LED est fournie au moyen d'une bobine (L1) et d'un commutateur (S1) cadencé, dans lequel, lorsque le commutateur (S1) est fermé, la bobine (L1) stocke temporairement une énergie qui se décharge à travers la LED lorsque le commutateur (S1) est ouvert, caractérisé en ce qu'un courant défini est injecté dans un enroulement secondaire (T2) d'un transformateur dont l'enroulement primaire (T1) est disposé en série par rapport à la LED, et en ce qu'au moins une mesure est effectuée du côté du secondaire afin de déterminer l'instant de fermeture du commutateur (S1), dans lequel on détecte l'instant de fermeture du commutateur (S1) lorsque le courant défini injecté atteint une valeur telle que le transformateur n'est plus à saturation du côté du primaire en raison du courant de LED (iLED).
EP10721272.2A 2009-04-30 2010-04-30 Circuit pour faire fonctionner des diodes luminescentes Not-in-force EP2425680B1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
AT2802009 2009-04-30
PCT/AT2010/000139 WO2010124313A2 (fr) 2009-04-30 2010-04-30 Circuit pour faire fonctionner des diodes luminescentes

Publications (2)

Publication Number Publication Date
EP2425680A2 EP2425680A2 (fr) 2012-03-07
EP2425680B1 true EP2425680B1 (fr) 2014-03-05

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EP10721272.2A Not-in-force EP2425680B1 (fr) 2009-04-30 2010-04-30 Circuit pour faire fonctionner des diodes luminescentes

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US (1) US8664873B2 (fr)
EP (1) EP2425680B1 (fr)
CN (1) CN102415214B (fr)
AT (1) AT508195B1 (fr)
DE (1) DE112010001827A5 (fr)
WO (1) WO2010124313A2 (fr)

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US9060406B2 (en) * 2009-04-14 2015-06-16 Tridonic Gmbh And Co Kg Power regulation of LED by means of an average value of the LED current and bidirectional counter
AT508195B1 (de) 2009-04-30 2012-03-15 Tridonic Gmbh & Co Kg Betriebsschaltung für leuchtdioden
JP6145980B2 (ja) * 2012-09-14 2017-06-14 東芝ライテック株式会社 照明装置
AT13981U1 (de) * 2013-04-30 2015-02-15 Tridonic Gmbh & Co Kg Betriebsschaltung für Leuchtdioden
AT14041U1 (de) * 2013-04-30 2015-03-15 Tridonic Gmbh & Co Kg Betriebsschaltung für Leuchtdioden mit Filterelement
AT14074U1 (de) 2013-04-30 2015-04-15 Tridonic Gmbh & Co Kg Betriebsschaltung für LED
CN103889127B (zh) * 2014-04-09 2015-12-02 魏其萃 无频闪线性led驱动模块及其工作方法
CN104201912B (zh) * 2014-08-15 2017-12-26 京东方科技集团股份有限公司 一种ac‑dc变换器、电源板和显示装置
DE102015214911A1 (de) * 2015-08-05 2017-02-09 Tridonic Gmbh & Co Kg Primärgetakteter, potentialgetrennter Wandler für LED-Konverter
US11039516B2 (en) 2017-11-13 2021-06-15 Signify Holding B.V. Solid state lighting circuit and control method

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JP4474562B2 (ja) * 2000-04-28 2010-06-09 東芝ライテック株式会社 発光ダイオード駆動装置
WO2003009653A1 (fr) * 2001-07-19 2003-01-30 Lumileds Lighting Us., Llc Dispositif de commutation de diode electroluminescente
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AT508195B1 (de) 2009-04-30 2012-03-15 Tridonic Gmbh & Co Kg Betriebsschaltung für leuchtdioden

Also Published As

Publication number Publication date
EP2425680A2 (fr) 2012-03-07
US20120104958A1 (en) 2012-05-03
WO2010124313A2 (fr) 2010-11-04
CN102415214A (zh) 2012-04-11
WO2010124313A3 (fr) 2011-05-26
AT508195B1 (de) 2012-03-15
CN102415214B (zh) 2014-12-10
DE112010001827A5 (de) 2012-05-31
AT508195A1 (de) 2010-11-15
US8664873B2 (en) 2014-03-04

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