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EP0156846A1 - Reduction a un minimum de la teneur en harmoniques pour des inverseurs a semi-conducteurs fonctionnant sur le secteur et attaquant des tubes a decharge gazeuse - Google Patents

Reduction a un minimum de la teneur en harmoniques pour des inverseurs a semi-conducteurs fonctionnant sur le secteur et attaquant des tubes a decharge gazeuse

Info

Publication number
EP0156846A1
EP0156846A1 EP84903468A EP84903468A EP0156846A1 EP 0156846 A1 EP0156846 A1 EP 0156846A1 EP 84903468 A EP84903468 A EP 84903468A EP 84903468 A EP84903468 A EP 84903468A EP 0156846 A1 EP0156846 A1 EP 0156846A1
Authority
EP
European Patent Office
Prior art keywords
output
switching
regulator
supply potential
potential
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Ceased
Application number
EP84903468A
Other languages
German (de)
English (en)
Other versions
EP0156846A4 (fr
Inventor
Mohammed Abdelmoneim Helal
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Minitronics Pty Ltd
Original Assignee
Minitronics Pty Ltd
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Minitronics Pty Ltd filed Critical Minitronics Pty Ltd
Publication of EP0156846A1 publication Critical patent/EP0156846A1/fr
Publication of EP0156846A4 publication Critical patent/EP0156846A4/fr
Ceased legal-status Critical Current

Links

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4225—Arrangements for improving power factor of AC input using a non-isolated boost converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/425—Arrangements for improving power factor of AC input using a single converter stage both for correction of AC input power factor and generation of a high frequency AC output voltage
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/42—Conversion of DC power input into AC power output without possibility of reversal
    • H02M7/44—Conversion of DC power input into AC power output without possibility of reversal by static converters
    • H02M7/48—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/538—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a push-pull configuration
    • H02M7/53803—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a push-pull configuration with automatic control of output voltage or current
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/42—Conversion of DC power input into AC power output without possibility of reversal
    • H02M7/44—Conversion of DC power input into AC power output without possibility of reversal by static converters
    • H02M7/48—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/539—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from DC by means of a converter, e.g. by high-voltage DC
    • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from DC by means of a converter, e.g. by high-voltage DC using static converters
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the present invention relates to solid state ballasts for fluorescent and gas discharge lamps, and in particular the invention provides a ballast wherein the current drawn from the mains has a reduced harmonic component when compared to prior art ballasts.
  • transformers it is a common practice to use transformers to provide power for electronic circuits from the mains supply. This method provides isolation, good regulation, protection from sudden mains fluctuations, and small harmonic distortion in the voltage waveform associated with the waveform of current drawn from the supply.
  • the disadvantages of using transformers in high power application is reflected in their size, weight and winding losses, and for these reasons users often elect to operate directly from the mains supply without employing a transformer.
  • a large magnetic choke placed before the full wave bridge can be used to filter out the higher harmonics of the current pulses while passing the fundamental component, however, such a choke introduces losses and is bulky.
  • a more practical approach is to use the full portion of the fully rectified mains voltage, for charging the capacitor. This can be achieved by using a switching regulator, in which case the current is distributed over a full cycle and is sinusoidal, and with this type of circuit it is possible to produce an output voltage which is higher than the peak input voltage.
  • the circuit of the present invention combines the function of a switching regulator with a half-bridge inverter to form a solid state ballast for fluorescent and HID lamps.
  • the disadvantage of each of the circuits described above is that the voltage across the load is essentially D.C, whereas the efficiency of fluorescent and gas discharge lamps increase with higher supply voltage frequencies and therefore an advantage can be gained by using an inverter to drive such lamps.
  • the present invention consists in a power converter, including rectification means to convert an alternating supply potential into a rectified supply potential, and inverter means connected across said rectified supply potential, said inverter means comprising an a.c. divider network having an output which substantially remains at a potential proportional to the rectified supply potential, a half-bridge switching circuit having an output from which alternating potential is produced, said alternating potential having a frequency.substantially higher than that of the supply potential, said switching circuit being coupled across the rectified supply potential at the frequency of said alternating potential but substantially isolated from the rectified supply potential at the frequency of the supply potential, storage means being connected across the switching circuit to maintain a substantially d.c. potential across the switching circuit thereby ensuring that said alternating potential is substantially constant in amplitude, the switching circuit output and the a.c. divider output defining respective sides of the output of said
  • the present invention also provides ,a solid state ballast which incorporates the power converter defined above.
  • the present invention consists in a switching regulator comprising rectification means to convert an alternating potential of an electrical supply into a rectified supply potential, an inductor and switching element connected in series across the rectified potential, a diode, the anode of which is connected to the junction of the inductor and the switching element and the cathode of which defines the output of the regulator, and storage means being connected across the regulator output, the switching element being controlled by a pulsed switching signal provided by a switching control circuit, the pulsed signal having a frequency which is controlled to increase with decreasing voltage at the regulator output, said regulator being characterised in that a parameter of the pulse signal is varied in response to the instantaneous rectified supply potential to control the waveform of the current flowing from the supply.
  • the pulse width is controlled to be inversely proportional to the input voltage and the frequency is proportional to the error in the output voltage, while in another embodiment the pulse width is constant and the frequency is proportional to both the input voltage and the output error voltage.
  • Figure 1 illustrates the circuit schematic of a first embodiment of the invention
  • Figure 2 graphically illustrates the current drawn by the circuit of Figure 1 when capacitor C 3 , is chosen to be too large
  • Figure 3 graphically illustrates the current drawn by the circuit of Figure 1 when capacitor C 3 , is correctly chosen
  • Figure 4 schematically illustrates a switching regulator according to a second form of the invention
  • Figure 5 illustrates several waveforms representing signal levels in the circuit of Figure 3 for (a) high and (b) reduced load conditions when both the pulse width and frequency are controlled;
  • Figure 6 illustrates similar waveforms to those of Figure 5 (a) and (b) for a system where only the pulse frequency is controlled;
  • FIG. 7 schematically illustrates the regulator of Figure 4 in greater detail
  • FIG. 8 schematically illustrates another embodiment of a regulator made in accordance with the present invention.
  • a solid state ballast of the present invention includes a bridge rectifier D1-D4 connected to the mains supply to produce a full-wave rectified voltage waveform between the points B and C.
  • a capacitor C is connected between the points B and C via a pair of diodes Dr and Dg, such that the capacitor C 3 , is isolated from the points B and C except when the voltage BC across these points exceeds the voltage across C 3 .
  • the voltage V-. chorus across C 3 is substantially constant with a small ripple due to the discharging of the capacitor C3 between the peaks in Verne c and the recharging of the capacitor C 3 when V_ c approaches its peak value.
  • a half bridge inverter circuit is connected between the points B, C, D and F and comprises a pair of capactiors C, and C 2 which form an AC voltage divider, and a pair of transistor switches Q- ⁇ and Q 2 which alternately switch on to apply either the potential at point D or that at point F to point A.
  • the AC divider is arranged to produce a voltage chorus c between points E and C which is substantially equal to 1/2 V ⁇ C , and as a result, the voltage V AE which forms the output of the inverter is a square wave having a peak to peak voltage swing equal to V Dp and the average value of said square wave being modulated by the voltage - V render c .
  • Each of capacitors C . and C 5 which are connected respectively across diodes D ⁇ and D g provides a high frequencybypass around its respective diode such that points D and F are isolated from points B and C by the diodes D 5 and Dg at the ripple frequency of V BC but are connected via C . and C 5 at the switching frequency of the transistors Q, and Q 2 ⁇
  • the switching frequency is 25 KHz, however, the value of this frequency is not essential to the operation of the circuit.
  • the inverter circuit also includes diodes D-, and D « which prevent the voltage V summon E between points B and E and the voltage réelle c between points E and C from becoming negative in value by more than one diode voltage drop, while diodes D réelle and D, Q serve to protect Q, and Q 2 from voltage polarity reversals between points D and A, and A and F respectively.
  • diodes D-, and D « which prevent the voltage V summon E between points B and E and the voltage réelle c between points E and C from becoming negative in value by more than one diode voltage drop
  • diodes D Volunteer and D, Q serve to protect Q, and Q 2 from voltage polarity reversals between points D and A, and A and F respectively.
  • the inverter output current flowing between points A and E is drawn, predominantly, from the mains via C 4 and C ⁇ each of which have a low impedance at the inverter switching frequency.
  • Capacitor C 3 which is an electrolytic capacitor, serves to maintain a substantially constant potential between the
  • C 3 and C 5 are chosen to suit the output load connected to the circuit and are selected such that the current drawn from the supply approaches a sinosoidal waveform.
  • Fig. 2 when C 3 is chosen to be too large the current drawn from the mains supply will have a sharp peak 10 during the period when capacitor C 3 is charging.
  • C 3 is chosen to be too large, the fall in capacitor voltage due to discharge through the inverter load is so small that the diodes D 5 and D g are only forward biased for a brief period at each peak of the full-wave rectified voltage V ⁇ C .
  • the capacitor C 3 must fully charge during this brief period, and as a larger capacitor will have a lower impedance the capacitor will be capable of charging at a sufficiently high rate to create a large peak in the current drawn from the supply.
  • inverter output current is drawn from both the mains supply and from C 3 such that the current drawn from the mains has a substantially sinusoidal waveform 11 and, referring to Fig. 3, when C 3 is correctly chosen the capacitor charging current 10 will not seriously affect the sinusoidal shape of the current waveform.
  • V_ p When C 3 is chosen to be too small the voltage V_ p will have excessive ripple, resulting in unacceptable variations in the peak to peak value of the square wave component of inverter output voltage V, E which in turn cause flicker in the light output at the lamp.
  • the inverter load comprises inductor L*., capactior Cg and a fluorescent lamp P.
  • Capacitor C g and inductor L have values which are chosen to allow the combination to resonate at the inverter switching frequency.
  • the capacitor Cg is bypassed by the tube and the inductor -, , serves to limit the current through the tube.
  • dimming of the lamp is readily achieved by reducing the supply voltage to the rectifier D,-D..
  • Figure 4 illustrates a circuit operated directly from the mains to produce a constant output d.c. voltage, and which can be used to supply the inverter for fluorescent lamps.
  • the circuit of Figure 4 draws a substantially sinusoidal current from the mains supply.
  • a switching regulator current control (SRCC) circuit produces pulses with period inversely proportional to the amplitudes of the full wave voltage and the frequency proportional to the output current drawn by the load 26.
  • the driving oscillator circuit monitors the D.C. voltage across the load via feedback line M, and adjusts its frequency accordingly to regulate the voltage, according to the load requirements.
  • Delivered output is proportional to the regulator frequency.
  • Stored energy in coil L 2 is proportional to the duration of the driver pulse and the amplitude of the applied voltage. Since amplitude of the input voltage varies as a full-wave, the switching pulse width is chosen to be larger during the initial portion of the full-wave and is reduced with increasing input voltage, throughout the full cycle, see (Fig. 5.). It should be noted that changing the number of pulse trains within a cycle does not affect the relationship of pulse width to the amplitude of the input voltage.
  • IC is used as an astable multi vibrator where the duration of each output pulse is determined by the time taken for capacitor C 33 to charge, this charging time being controlled by the series resistor combination 3, R and transistor Q 3 which is driven directly from the fully rectified wave at node G, via resistor R3g- To correct for the phase shifting effect of the signal at node J, due to base-emitter junction capacitance of Q33, a series network consisting of R37, C3J, is put in parallel with R33.
  • One such network consists of R.,, R 33 and D 35 providing a "fast” response, while the other consists of R32' R 34' R 35 an ⁇ c 36 P rov • ⁇ *•--•- ng a "slow” response.
  • Slow variations of the d.c. voltage on node M are monitored by the latter network consisting of C3 , R 32 R 4 and R 3 _, so that an increase in V, effectively drives Q3, further into the "ON" state.
  • transistor Q 32 is driven into the "off” state, increasing the discharge rate of capacitor C33, which reduces the frequency of the inverter, and V. is reduced accordingly to a steady value.
  • V Sudden variations in V, can be expected such as when the load is removed.
  • the network consisting of R31, R33 and D 35 monitors such disturbances and regulates V, accordingly.
  • R 46 and D 3 g ensure that Q 32 is “OFF" while signal on pin 3 is “high”, thus the charging period of C3 is made totally independent of the discharge period.
  • Q34, L 31 and D 3 g step up the full-wave at node G into the required, voltage according to the signal on node L of the system described.
  • the hard wired Switching Regulator Current Control Circuit is replaced by a Microprocessor based SRCC circuit wherein the modulation voltage V warrant and the feedback voltage V render are connected to the inputs-of an analog to digital convertion (ADC) 101 which allows these signals to be monitored by the Micoprocessor (UP) 102.
  • the microprocessor 102 calculates the required pulse width and frequency parameters and uses these to control the Pulse Width Modulator (PWM) 103 in order to produce the SRCC output signal V L which drives transistor Q 55 via resistor R ⁇ .
  • PWM Pulse Width Modulator
  • the processor is also provided with a serial I/O 5 communications port Dg which can be used to remotely control the SRCC while various other control voltage inputs and control I/O circuits are provided to enable flexible usage of the regulator.

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Inverter Devices (AREA)
  • Circuit Arrangements For Discharge Lamps (AREA)
  • Dc-Dc Converters (AREA)
  • Power Conversion In General (AREA)

Abstract

Un convertisseur est prévu pour la conversion de la puissance électrique à la fréquence du secteur en une puissance de fréquence supérieure, préférable pour l'attaque de tubes à décharge gazeuse. Le convertisseur comporte un inverseur en demi-ponts (Q1 et Q2) relié par un condensateur à filtre (C3) d'une alimentation redressée filtrée, qui est isolé efficacement du redresseur (D1-D4) à la fréquence du secteur par des diodes d'isolation (D5, D6) qui sont en polarisation inverse pour la majorité du cycle de fréquence du secteur, lorsque le condensateur à filtre (C3) est entièrement chargé. Les diodes d'isolation (D5, D6) sont dérivées par des condensateurs (C4, C5) à la fréquence de commutation de l'inverseur, si bien qu'une certaine partie du courant de sortie de l'inverseur est tirée directement de l'alimentation plutôt que du condensateur à filtre (C3). La voie de retour du courant de sortie de l'inverseur passe par le réseau de division de courant alternatif (C1, C2). Une inductance (L1) est prévue pour limiter le courant en direction du tube (P), alors qu'un condensateur (C6) est monté en série avec les fils chauffants du tube (P) afin de fournir un courant de chauffage pendant l'amorçage. Conformément à une autre caractéristique de la présente invention, un régulateur de commutation est prévu où un circuit de commande de régulateur de commutation (SRCC) attaque l'élément de commutation (Q2) d'un circuit de régulateur de commutation et la fréquence de la sortie du circuit de commande de régulateur de commutation (SRCC) est régulée afin de maintenir la tension de sortie (M) du régulateur de commutation à un niveau essentiellement constant, alors que la largeur d'impulsion de la sortie du circuit de commande de régulateur de commutation (SRCC) est régulée en réponse à la tension d'alimentation redressée instantanée (N), si bien que le courant (I) tiré par le régulateur est essentiellement sinusoïdal.
EP19840903468 1983-09-19 1984-09-19 Reduction a un minimum de la teneur en harmoniques pour des inverseurs a semi-conducteurs fonctionnant sur le secteur et attaquant des tubes a decharge gazeuse. Ceased EP0156846A4 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
AU1475/83 1983-09-19
AUPG147583 1983-09-19

Publications (2)

Publication Number Publication Date
EP0156846A1 true EP0156846A1 (fr) 1985-10-09
EP0156846A4 EP0156846A4 (fr) 1986-02-13

Family

ID=3770324

Family Applications (1)

Application Number Title Priority Date Filing Date
EP19840903468 Ceased EP0156846A4 (fr) 1983-09-19 1984-09-19 Reduction a un minimum de la teneur en harmoniques pour des inverseurs a semi-conducteurs fonctionnant sur le secteur et attaquant des tubes a decharge gazeuse.

Country Status (12)

Country Link
EP (1) EP0156846A4 (fr)
JP (1) JPS61500045A (fr)
AU (1) AU567769B2 (fr)
BR (1) BR8407088A (fr)
DK (1) DK220985A (fr)
FI (1) FI852011L (fr)
GB (1) GB2147159B (fr)
IN (1) IN162395B (fr)
IT (1) IT1179431B (fr)
NZ (1) NZ209570A (fr)
WO (1) WO1985001400A1 (fr)
ZA (1) ZA847317B (fr)

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Publication number Publication date
IN162395B (fr) 1988-05-21
GB2147159A (en) 1985-05-01
JPS61500045A (ja) 1986-01-09
IT8448872A0 (it) 1984-09-18
ZA847317B (en) 1985-06-26
DK220985D0 (da) 1985-05-17
IT1179431B (it) 1987-09-16
AU567769B2 (en) 1987-12-03
AU3430584A (en) 1985-04-11
FI852011A0 (fi) 1985-05-20
NZ209570A (en) 1988-03-30
GB2147159B (en) 1987-06-10
FI852011A7 (fi) 1985-05-20
EP0156846A4 (fr) 1986-02-13
IT8448872A1 (it) 1986-03-18
BR8407088A (pt) 1985-08-13
GB8423475D0 (en) 1984-10-24
DK220985A (da) 1985-05-17
FI852011L (fi) 1985-05-20
WO1985001400A1 (fr) 1985-03-28

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