CN102315873B - Cross polarization antenna system reception merging method and apparatus thereof - Google Patents

Abstract

An embodiment of the invention provides a cross polarization antenna system reception merging method and an apparatus thereof to overcome problems of large amount of computation of hardware and low processing efficiency in the prior art. The method comprises the following steps: dividing a cross polarization antenna into antenna subarrays according to a polarization direction; carrying out weight matrix calculation on each antenna subarray respectively, and carrying out normalization coefficient calculation on the corresponding antenna subarrays by utilizing a weight matrix; carrying out channel equalization on a non-pilot signal received by the corresponding antenna subarrays by utilizing the weight matrix to obtain an equalization result; according to the equalization result and a normalization coefficient of the antenna subarrays, carrying out antenna array merging and normalization coefficient adjustment to obtain a merging result of the non-pilot signal. In reception and merging, the cross polarization antenna is divided into the antenna subarrays according to the polarization direction, and carrying out an inverse operation on a high dimension matrix is avoided. Hardware can carry out same calculation processing on each subarray, amount of computation is reduced, and processing efficiency is raised.

Description

Receiving and combining method and device for cross polarization antenna system

Technical Field

The present invention relates to the field of wireless communication technologies, and in particular, to a receiving and combining method and device for a cross-polarized antenna system.

Background

Diversity reception is one of the key technologies of MIMO (Multiple-Input Multiple-Output), and mainly means that Multiple antennas receive Multiple independent signal copies carrying the same information from Multiple channels, and since the independent signal copies cannot be in a deep fading condition at the same time, at least one signal copy with sufficient strength can be guaranteed to be provided for a receiver at any given moment, thereby improving the signal-to-noise ratio of the received signal.

The multiple independent signal copies are diversity received and combined by the cross-polarized antenna system. The cross polarization antenna system comprises a plurality of cross polarization antennas, and when the number of the cross polarization antennas is large, the calculation amount required by hardware is large, and the processing efficiency is low.

Disclosure of Invention

In view of this, embodiments of the present invention provide a method and an apparatus for receiving and combining cross-polarized antenna systems, so as to overcome the problems of large hardware computation and low processing efficiency in the prior art.

In order to achieve the purpose, the invention provides the following technical scheme:

a cross-polarized antenna system receiving and combining method comprises the following steps:

dividing cross polarization antennas in the cross polarization antenna system into antenna sub-arrays according to polarization directions, wherein each antenna sub-array comprises array elements with the same polarization directions;

respectively carrying out weight matrix calculation on each antenna subarray, and carrying out normalization coefficient calculation on the corresponding antenna subarrays by using the weight matrix;

carrying out channel equalization on the non-pilot signals received by the corresponding antenna subarrays by using the weight matrix to obtain an equalization result;

and according to the equalization result and the normalization coefficient of the antenna subarray, carrying out antenna array combination and normalization coefficient adjustment to obtain a combination result of the non-pilot signals.

A cross-polarized antenna system receive combining apparatus comprising:

a cross-polarized antenna for receiving an uplink signal;

the antenna subarray distribution unit is used for dividing the cross polarization antenna into antenna subarrays according to the polarization direction, and each antenna subarray comprises array elements with the same polarization direction;

the weight calculation unit is used for respectively calculating a weight matrix of each antenna subarray;

the normalization coefficient calculation unit is used for calculating the normalization coefficient of the corresponding antenna subarrays by utilizing the weight matrix calculated by the weight calculation unit;

the antenna subarray equalization calculation unit is used for carrying out channel equalization on the non-pilot signals received by the corresponding antenna subarrays by utilizing the weight matrix to obtain an equalization result;

and the adjusting unit is used for carrying out antenna array combination and normalization coefficient adjustment according to the equalization result and the normalization coefficient of the antenna subarray to obtain a combination result of the non-pilot signals.

According to the technical scheme, when receiving and combining, the cross polarization antenna is divided into the antenna sub-arrays according to the polarization direction, inversion operation on a high-dimensional matrix is avoided, and matrix decomposition is carried out on a low-dimensional matrix. In this case, the hardware can perform the same calculation process on each subarray, thereby reducing the amount of calculation and improving the processing efficiency.

Drawings

In order to more clearly illustrate the embodiments of the present invention or the technical solutions in the prior art, the drawings used in the description of the embodiments or the prior art will be briefly described below, it is obvious that the drawings in the following description are only embodiments of the present invention, and for those skilled in the art, other drawings can be obtained according to the provided drawings without creative efforts.

Fig. 1 is a flow chart of a receiving and combining method of a cross-polarized antenna system according to an embodiment of the present invention;

fig. 2 is another flowchart of a receiving and combining method of a cross-polarized antenna system according to an embodiment of the present invention;

fig. 3 is a schematic structural diagram of a receiving and combining device of a cross-polarized antenna system according to an embodiment of the present invention;

fig. 4 is another schematic structural diagram of a receiving and combining device of a cross-polarized antenna system according to an embodiment of the present invention;

fig. 5 is a schematic structural diagram of a receiving and combining apparatus of a cross-polarized antenna system according to an embodiment of the present invention;

fig. 6 is a schematic structural diagram of an eight-antenna system according to an embodiment of the present invention;

fig. 7 is a schematic diagram of a partitioned antenna subarray of an eight-antenna system according to an embodiment of the present invention;

fig. 8 is a schematic diagram of an eight-antenna based system according to an embodiment of the present invention;

fig. 9 is a flowchart of a receiving and combining method of a cross-polarized antenna system according to an embodiment of the present invention;

fig. 10 is a schematic diagram of calculations within the antenna sub-array based on fig. 9;

fig. 11 is a schematic structural diagram of another receiving and combining device of a cross-polarized antenna system according to an embodiment of the present invention.

Detailed Description

For the sake of reference and clarity, the descriptions, abbreviations or abbreviations of the technical terms used hereinafter are summarized as follows:

PRB: physical Resource Block, Physical Resource Block;

LTE: long Term Evolution, Long Term Evolution;

OFDM: orthogonal Frequency Division Multiplexing, Frequency Division Multiplexing;

MIMO: Multiple-Input Multiple-Output.

The technical solutions in the embodiments of the present invention will be clearly and completely described below with reference to the drawings in the embodiments of the present invention, and it is obvious that the described embodiments are only a part of the embodiments of the present invention, and not all of the embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.

The 3GPP LTE adopts advanced wireless transmission technologies such as OFDM and MIMO (Multiple-Input Multiple-Output), a flat network structure and an all-IP system architecture, and is a new-generation mobile communication technology with a higher peak rate and a shorter transmission delay. The reliability requirement is remarkably improved while high-speed data transmission is carried out, and higher data transmission reliability is also required particularly under severe natural environment.

The basic starting point of the MIMO technology is to decompose user data into multiple parallel data streams, transmit the data streams simultaneously by multiple transmitting antennas within a specified bandwidth, and then receive the data streams by multiple receiving antennas. And finally restoring the original data stream by utilizing a demodulation technology according to the spatial characteristics of each parallel data stream.

To combat the larger time-varying fading and multipath interference and improve transmission reliability, diversity reception techniques are commonly used. Diversity reception is one of the key techniques of MIMO, and mainly means that multiple antennas receive multiple independent signal copies carrying the same information from multiple channels, and since the independent signal copies cannot be in a deep fading condition at the same time, at least one signal copy with sufficient strength can be guaranteed to be provided for a receiver at any given time, thereby improving the signal-to-noise ratio of the received signal.

The multiple independent signal copies are diversity received and combined by the cross-polarized antenna system. The cross polarization antenna system comprises a plurality of cross polarization antennas, and when the number of the cross polarization antennas is large, the calculation amount of hardware is large, and the processing efficiency is low.

In order to solve the above problem, an embodiment of the present invention provides a cross-polarized antenna system receiving and combining method, referring to fig. 1 and fig. 2, the method at least includes:

s1, dividing cross polarization antennas in the cross polarization antenna system into antenna sub-arrays according to the polarization direction, wherein each antenna sub-array comprises array elements with the same polarization direction;

s2, respectively carrying out weight matrix calculation on each antenna subarray, and carrying out normalization coefficient calculation on the corresponding antenna subarrays by using the weight matrix;

in a specific implementation, step S2 can be subdivided into:

and S21, obtaining a normalization coefficient by multiplying the conjugate transpose of the weight matrix and a channel coefficient matrix obtained by channel estimation.

S3, performing channel equalization on the non-pilot signals received by the corresponding antenna subarrays by using the weight matrix to obtain an equalization result;

it should be noted that the non-pilot signal may be formed by a non-pilot subcarrier data matrix. Thus, in a specific implementation, step S3 may be subdivided into:

and S31, multiplying the conjugate transpose of the weight matrix by the non-pilot subcarrier data matrix received by the antenna subarray to obtain the equalization result.

And S4, according to the equalization result and the normalization coefficient of the antenna subarray, carrying out antenna array combination and normalization coefficient adjustment to obtain a combination result of the non-pilot signals. The combined result of the non-pilot signals is the final received combined signal.

In other embodiments of the present invention, step S4 may specifically include the following steps:

s41, summing the equalization results of each antenna subarray to obtain a total equalization result;

s42, summing the normalization coefficients of the antenna subarrays to obtain a total normalization coefficient;

and S43, dividing the total equalization result by the total normalization coefficient to obtain a combination result of the non-pilot signals.

In other embodiments of the present invention, if the Maximum Ratio Combining (MRC) algorithm is adopted, the weight matrix in the above embodiments may be obtained by: and obtaining the conjugate transpose of the channel coefficient matrix obtained by the channel estimation as the conjugate transpose of the weight matrix.

And if the Interference Rejection Combining (IRC) algorithm is followed, the weight matrix in the above embodiment may be obtained by: and multiplying the conjugate transpose of the channel coefficient matrix obtained by the channel estimation by the inverse matrix of the covariance matrix of the interference and noise signals of the corresponding antenna subarray to obtain the conjugate transpose of the weight matrix.

The covariance matrix of the interference and noise signals can be obtained by calculating the statistical average after multiplying the interference and noise signal matrix by the conjugate transpose of the interference and noise signal matrix.

As for the interference plus noise signal matrix, it can be obtained either by the prior art or by:

after the pilot signal received by the antenna subarray is used as a reference signal to perform complex correlation with a local reference signal, a channel coefficient matrix containing interference and noise signals is obtained;

and subtracting the channel coefficient matrix containing the interference and noise signals from the channel coefficient matrix obtained by channel estimation to obtain the interference and noise signal matrix.

Correspondingly, an embodiment of the present invention further provides a receiving and combining apparatus for a cross-polarized antenna system, and fig. 3 shows a structure of the receiving and combining apparatus, including:

a cross-polarized antenna 1 for receiving an uplink signal;

the antenna subarray distribution unit 2 is used for dividing cross polarization antennas in the cross polarization antenna system into antenna subarrays according to polarization directions, and each antenna subarray comprises array elements with the same polarization direction;

a weight calculation unit 3, configured to perform weight matrix calculation on each antenna subarray;

the normalization coefficient calculation unit 4 is used for calculating the normalization coefficient of the corresponding antenna subarrays by using the weight matrix calculated by the weight calculation unit 3;

the antenna subarray equalization calculating unit 5 is used for performing channel equalization on the non-pilot signals received by the corresponding antenna subarrays by using the weight matrixes to obtain an equalization result;

and an adjusting unit 6, configured to perform antenna array combination and normalization coefficient adjustment according to the equalization result and the normalization coefficient of the antenna subarray, so as to obtain a combination result of the non-pilot signals.

In another embodiment of the present invention, referring to fig. 4, the adjusting unit 6 may include:

the equalization result merging unit 7 is used for summing the equalization results of each antenna subarray to obtain a total equalization result;

a normalization coefficient combining unit 8, configured to sum the normalization coefficients of the antenna subarrays to obtain a total normalization coefficient;

and a division calculating unit 9, configured to divide the total equalization result by the total normalization coefficient to obtain a combination result of the non-pilot signals.

As mentioned above, the weight matrix calculation can be performed by:

taking the conjugate transpose of the channel coefficient matrix obtained by channel estimation as the conjugate transpose of the weight matrix; or,

multiplying the conjugate transpose of the channel coefficient matrix obtained by channel estimation by the inverse matrix of the covariance matrix of the interference-plus-noise signal of the corresponding antenna subarray to obtain the conjugate transpose of the weight matrix;

the covariance matrix of the interference and noise signals is obtained by calculating the statistical average after multiplying the interference and noise signal matrix by the conjugate transpose of the interference and noise signal matrix.

While according to the IRC algorithm, referring to fig. 5, the apparatus in all the above embodiments may further include an interference plus noise signal calculation unit 10 and a channel coefficient matrix calculation unit 11, wherein:

a channel coefficient matrix calculation unit 10, configured to perform complex correlation between a local reference signal and a pilot signal received by an antenna subarray to obtain a channel coefficient matrix containing interference plus noise signals;

and an interference and noise signal calculation unit 11, configured to subtract the channel coefficient matrix containing the interference and noise signal from the channel coefficient matrix obtained through channel estimation to obtain the interference and noise signal matrix.

For convenience of understanding, the technical solution of the present invention will be further described by taking an eight-antenna system at the receiving end of the base station as an example. Fig. 6 shows a configuration of an eight antenna system comprising array elements 1-8.

Assuming that the transmitting end is 1 antenna and the receiving end is an N (in this embodiment, N is 8) antenna system, the received signal model can be expressed as:

r＝hx+n

wherein: r is the received signal of nx 1, x represents the transmitted signal, h is the channel coefficient of nx 1, and N is the interference plus noise signal of nx 1.

And the receiving end combined signal can be expressed as:

y＝w^Hr, i.e. y ═ w^H(hx + n), y denotes the combined signal, w denotes the weight vector, and the superscript H denotes the conjugate transpose.

In solving for w, the IRC algorithm is based on the maximum signal to interference plus noise power ratio (MSINR) criterion. According to this criterion the following formula:

$\mathrm{SINR}=\frac{E\left[\left(w^H\mathrm{hx}\right){\left(w^H\mathrm{hx}\right)}^H\right]}{E\left[\left(w^{H}n\right){\left(w^{H}n\right)}^H\right]}=\frac{w^H{\mathrm{hh}}^{H}w}{w^{H}E\left[{\mathrm{nn}}^H\right]w}$

here we assume that the transmitted signal energy is normalized, i.e.: e [ xx)^H]I is an identity matrix. R ═ E [ nn ]^H]A covariance matrix that is the interference plus noise signal. Wherein, E [. C]Representing the calculation of a statistical average over the matrix.

The above formula can be:

$\mathrm{SINR}=\frac{w^H{\mathrm{hh}}^{H}w}{w^H\mathrm{Rw}}$

according to the generalized Rayleigh theorem, when w is the matrix R^-1hh^HWhen the feature vector corresponding to the maximum feature value is obtained, the SINR is maximum, and finally, the maximum feature value can be obtainedThe weight matrix is: w is a^H＝h^HR^-1(superscript-1 denotes the matrix inversion operation).

For an eight antenna system n is an 8 x 1 matrix and R is an 8 x 8 matrix. When colored interference exists, the interference suppression combination algorithm can effectively suppress the interference, but in the prior art, the covariance matrix of the interference and noise signals is difficult to estimate accurately (in the prior art, the covariance matrix of the interference and noise signals is estimated by directly adopting the autocorrelation matrix of the received signals approximately), and meanwhile, when the dimension of the eight-antenna matrix is 8, the matrix inversion operation has a large operation amount. The technical scheme of the invention can solve the problems and please refer to the following contents in detail.

When the w is solved, if the interference is not considered or treated as white noise according to the MRC algorithm, the covariance matrix R only has elements on the diagonal line, other elements are 0, and R is sigma²I(σ²As the noise power). Ignoring coefficients the weights can be abbreviated as: w is a^H＝h^H。

After the IRC algorithm and MRC algorithm are introduced, the core idea of the technical scheme based on the eight-antenna system is introduced:

according to the IRC algorithm, the interference between different polarization directions is neglected, and the interference-plus-noise covariance matrix R can be simplified into a block diagonal matrix, i.e.: <math> <mrow> <mi>R</mi> <mo>=</mo> <mfenced open='[' close=']'> <mtable> <mtr> <mtd> <msubsup> <mi>R</mi> <mrow> <mn>4</mn> <mo>&times;</mo> <mn>4</mn> </mrow> <mi>h</mi> </msubsup> </mtd> <mtd> <mn>0</mn> </mtd> </mtr> <mtr> <mtd> <mn>0</mn> </mtd> <mtd> <msubsup> <mi>R</mi> <mrow> <mn>4</mn> <mo>&times;</mo> <mn>4</mn> </mrow> <mi>v</mi> </msubsup> </mtd> </mtr> </mtable> </mfenced> </mrow> </math> (superscripts h, v denote polarization aspects, respectively), which can then be deduced to yield:

$y=\frac{w^{H}r}{w^{H}h}=\frac{h^H{R}^{-1}r}{h^H{R}^{-1}h}=\frac{w_1{\mathrm{<figure-callout\; id="1"\; label="r"\; filenames="HDA0000089610820000031.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">r</figure-callout>}}_1+w_2{\mathrm{<figure-callout\; id="2"\; label="r"\; filenames="HDA0000089610820000031.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">r</figure-callout>}}_2+w_3{\mathrm{<figure-callout\; id="3"\; label="r"\; filenames="HDA0000089610820000031.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">r</figure-callout>}}_3+w_4{\mathrm{<figure-callout\; id="4"\; label="r"\; filenames="HDA0000089610820000042.png,HDA0000089610820000051.png"\; state="\{\{state\}\}">r</figure-callout>}}_4+w_5{\mathrm{<figure-callout\; id="5"\; label="r"\; filenames="HDA0000089610820000031.png,HDA0000089610820000051.png"\; state="\{\{state\}\}">r</figure-callout>}}_5+w_6{\mathrm{<figure-callout\; id="6"\; label="r"\; filenames="HDA0000089610820000042.png,HDA0000089610820000051.png"\; state="\{\{state\}\}">r</figure-callout>}}_6+w_7{\mathrm{<figure-callout\; id="7"\; label="r"\; filenames="HDA0000089610820000042.png,HDA0000089610820000051.png"\; state="\{\{state\}\}">r</figure-callout>}}_7{+w}_8{r}_8}{w_1{\mathrm{<figure-callout\; id="1"\; label="h"\; filenames="HDA0000089610820000031.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">h</figure-callout>}}_1+w_2{\mathrm{<figure-callout\; id="2"\; label="h"\; filenames="HDA0000089610820000031.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">h</figure-callout>}}_2+w_3{\mathrm{<figure-callout\; id="3"\; label="h"\; filenames="HDA0000089610820000031.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">h</figure-callout>}}_3+w_4{\mathrm{<figure-callout\; id="4"\; label="h"\; filenames="HDA0000089610820000042.png,HDA0000089610820000051.png"\; state="\{\{state\}\}">h</figure-callout>}}_4+w_5{\mathrm{<figure-callout\; id="5"\; label="h"\; filenames="HDA0000089610820000031.png,HDA0000089610820000051.png"\; state="\{\{state\}\}">h</figure-callout>}}_5+w_6{\mathrm{<figure-callout\; id="6"\; label="h"\; filenames="HDA0000089610820000042.png,HDA0000089610820000051.png"\; state="\{\{state\}\}">h</figure-callout>}}_6+w_7{\mathrm{<figure-callout\; id="7"\; label="h"\; filenames="HDA0000089610820000042.png,HDA0000089610820000051.png"\; state="\{\{state\}\}">h</figure-callout>}}_7+w_8{\mathrm{<figure-callout\; id="8"\; label="h"\; filenames="HDA0000089610820000032.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">h</figure-callout>}}_8}$

$=\frac{(w_1{\mathrm{<figure-callout\; id="1"\; label="r"\; filenames="HDA0000089610820000031.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">r</figure-callout>}}_1+w_2{\mathrm{<figure-callout\; id="2"\; label="r"\; filenames="HDA0000089610820000031.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">r</figure-callout>}}_2+w_3{\mathrm{<figure-callout\; id="3"\; label="r"\; filenames="HDA0000089610820000031.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">r</figure-callout>}}_3+w_4{r}_4)+(w_5{\mathrm{<figure-callout\; id="5"\; label="r"\; filenames="HDA0000089610820000031.png,HDA0000089610820000051.png"\; state="\{\{state\}\}">r</figure-callout>}}_5+w_6{\mathrm{<figure-callout\; id="6"\; label="r"\; filenames="HDA0000089610820000042.png,HDA0000089610820000051.png"\; state="\{\{state\}\}">r</figure-callout>}}_6+w_7{\mathrm{<figure-callout\; id="7"\; label="r"\; filenames="HDA0000089610820000042.png,HDA0000089610820000051.png"\; state="\{\{state\}\}">r</figure-callout>}}_7+w_8{r}_8)}{(w_1{\mathrm{<figure-callout\; id="1"\; label="h"\; filenames="HDA0000089610820000031.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">h</figure-callout>}}_1+w_2{\mathrm{<figure-callout\; id="2"\; label="h"\; filenames="HDA0000089610820000031.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">h</figure-callout>}}_2+w_3{\mathrm{<figure-callout\; id="3"\; label="h"\; filenames="HDA0000089610820000031.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">h</figure-callout>}}_3+w_4{h}_4)+(w_5{\mathrm{<figure-callout\; id="5"\; label="h"\; filenames="HDA0000089610820000031.png,HDA0000089610820000051.png"\; state="\{\{state\}\}">h</figure-callout>}}_5+w_6{\mathrm{<figure-callout\; id="6"\; label="h"\; filenames="HDA0000089610820000042.png,HDA0000089610820000051.png"\; state="\{\{state\}\}">h</figure-callout>}}_6+w_7{\mathrm{<figure-callout\; id="7"\; label="h"\; filenames="HDA0000089610820000042.png,HDA0000089610820000051.png"\; state="\{\{state\}\}">h</figure-callout>}}_7+w_8{h}_8)}.$

similarly, according to the MRC algorithm:

$y=\frac{w^{H}r}{w^{H}h}=\frac{h^{H}r}{h^{H}h}=\frac{w_1{\mathrm{<figure-callout\; id="1"\; label="r"\; filenames="HDA0000089610820000031.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">r</figure-callout>}}_1+w_2{\mathrm{<figure-callout\; id="2"\; label="r"\; filenames="HDA0000089610820000031.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">r</figure-callout>}}_2+w_3{\mathrm{<figure-callout\; id="3"\; label="r"\; filenames="HDA0000089610820000031.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">r</figure-callout>}}_3+w_4{\mathrm{<figure-callout\; id="4"\; label="r"\; filenames="HDA0000089610820000042.png,HDA0000089610820000051.png"\; state="\{\{state\}\}">r</figure-callout>}}_4+w_5{\mathrm{<figure-callout\; id="5"\; label="r"\; filenames="HDA0000089610820000031.png,HDA0000089610820000051.png"\; state="\{\{state\}\}">r</figure-callout>}}_5+w_6{\mathrm{<figure-callout\; id="6"\; label="r"\; filenames="HDA0000089610820000042.png,HDA0000089610820000051.png"\; state="\{\{state\}\}">r</figure-callout>}}_6+w_7{\mathrm{<figure-callout\; id="7"\; label="r"\; filenames="HDA0000089610820000042.png,HDA0000089610820000051.png"\; state="\{\{state\}\}">r</figure-callout>}}_7{+w}_8{r}_8}{w_1{\mathrm{<figure-callout\; id="1"\; label="h"\; filenames="HDA0000089610820000031.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">h</figure-callout>}}_1+w_2{\mathrm{<figure-callout\; id="2"\; label="h"\; filenames="HDA0000089610820000031.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">h</figure-callout>}}_2+w_3{\mathrm{<figure-callout\; id="3"\; label="h"\; filenames="HDA0000089610820000031.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">h</figure-callout>}}_3+w_4{\mathrm{<figure-callout\; id="4"\; label="h"\; filenames="HDA0000089610820000042.png,HDA0000089610820000051.png"\; state="\{\{state\}\}">h</figure-callout>}}_4+w_5{\mathrm{<figure-callout\; id="5"\; label="h"\; filenames="HDA0000089610820000031.png,HDA0000089610820000051.png"\; state="\{\{state\}\}">h</figure-callout>}}_5+w_6{\mathrm{<figure-callout\; id="6"\; label="h"\; filenames="HDA0000089610820000042.png,HDA0000089610820000051.png"\; state="\{\{state\}\}">h</figure-callout>}}_6+w_7{\mathrm{<figure-callout\; id="7"\; label="h"\; filenames="HDA0000089610820000042.png,HDA0000089610820000051.png"\; state="\{\{state\}\}">h</figure-callout>}}_7+w_8{\mathrm{<figure-callout\; id="8"\; label="h"\; filenames="HDA0000089610820000032.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">h</figure-callout>}}_8}$

$=\frac{(w_1{\mathrm{<figure-callout\; id="1"\; label="r"\; filenames="HDA0000089610820000031.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">r</figure-callout>}}_1+w_2{\mathrm{<figure-callout\; id="2"\; label="r"\; filenames="HDA0000089610820000031.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">r</figure-callout>}}_2+w_3{\mathrm{<figure-callout\; id="3"\; label="r"\; filenames="HDA0000089610820000031.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">r</figure-callout>}}_3+w_4{r}_4)+(w_5{\mathrm{<figure-callout\; id="5"\; label="r"\; filenames="HDA0000089610820000031.png,HDA0000089610820000051.png"\; state="\{\{state\}\}">r</figure-callout>}}_5+w_6{\mathrm{<figure-callout\; id="6"\; label="r"\; filenames="HDA0000089610820000042.png,HDA0000089610820000051.png"\; state="\{\{state\}\}">r</figure-callout>}}_6+w_7{\mathrm{<figure-callout\; id="7"\; label="r"\; filenames="HDA0000089610820000042.png,HDA0000089610820000051.png"\; state="\{\{state\}\}">r</figure-callout>}}_7+w_8{r}_8)}{(w_1{\mathrm{<figure-callout\; id="1"\; label="h"\; filenames="HDA0000089610820000031.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">h</figure-callout>}}_1+w_2{\mathrm{<figure-callout\; id="2"\; label="h"\; filenames="HDA0000089610820000031.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">h</figure-callout>}}_2+w_3{\mathrm{<figure-callout\; id="3"\; label="h"\; filenames="HDA0000089610820000031.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">h</figure-callout>}}_3+w_4{h}_4)+(w_5{\mathrm{<figure-callout\; id="5"\; label="h"\; filenames="HDA0000089610820000031.png,HDA0000089610820000051.png"\; state="\{\{state\}\}">h</figure-callout>}}_5+w_6{\mathrm{<figure-callout\; id="6"\; label="h"\; filenames="HDA0000089610820000042.png,HDA0000089610820000051.png"\; state="\{\{state\}\}">h</figure-callout>}}_6+w_7{\mathrm{<figure-callout\; id="7"\; label="h"\; filenames="HDA0000089610820000042.png,HDA0000089610820000051.png"\; state="\{\{state\}\}">h</figure-callout>}}_7+w_8{h}_8)}.$

based on the above formula, referring to fig. 7 and 8, the array elements 1-8 of the eight-antenna system can be divided into two antenna sub-arrays: the array elements 1, 2, 3 and 4 with the polarization direction of-45 degrees form an antenna sub-array 1, and the array elements 5, 6, 7 and 8 with the polarization direction of +45 degrees form an antenna sub-array 2.

Let the signal received by the Kth element of the ith antenna sub-array be r_i，K(i-1, 2; K-1, 4), wherein r_1，1To r_1，4Respectively correspond to the array elements 1-4 in sequence, r_2，1To r_2，4Corresponding to the array elements 5-8 in turn, and the weight value corresponding to each array element is w_i，K. The invention respectively carries out channel equalization on each antenna subarray to obtain an equalization result y₁And y₂And obtaining normalized coefficients scale1 and scale2 of the two antenna sub-arrays, and then summing the equalization results of the antenna sub-arrays to obtain a total equalization result y₀And summing the normalization coefficients of the antenna subarrays to obtain a total normalization coefficient, and dividing the total equalization result by the total normalization coefficient to obtain a combined signal y.

Based on the above core idea, referring to fig. 9 and 10 (fig. 10 is a calculation in an antenna sub-array), the present embodiment includes the following steps:

s901: the array element in the cross polarization antenna system at the receiving end of the base station is divided into two antenna sub-arrays in-45-degree polarization direction and + 45-degree polarization direction.

S902: and calculating interference and noise signals on the pilot symbol subcarriers of the physical resource block of each antenna subarray.

In a specific implementation, the following formula can be used: n is_K，j＝h_K，j-h_{K，j_est}；

Where k represents an array element number of a receiving end of the base station, and in this embodiment, the value is 1, 2, 3, 4, and j is a frequency domain subcarrier number, and in this embodiment, the value is 1 to 12.

h_{K，j_est}The channel coefficient on the jth subcarrier of the Kth array element obtained by channel estimation is obtained. And h_K，jIn contrast, h_{K，j_est}Is to remove the over-interference plus noise.

h_K，jThe specific calculation formula of the channel coefficient containing the interference plus noise signal obtained by performing complex correlation on the received pilot signal (reference signal) and the local reference signal is as follows:

h_K，j＝rs_K，j×dmrs_K，j ^*

wherein denotes the conjugation, rs_K，jDenotes the received reference signal, dmrs_K，jFor locally generated reference signals for demodulation.

In addition, in wireless communication, control signals for ensuring normal operation of the system are transmitted in addition to useful signals. The pilot signal is generally used in terms of ensuring system synchronization, channel estimation, and the like. The signals received by the antenna sub-array comprise pilot signals and non-pilot signals, the non-pilot signals carrying useful information.

As shown in fig. 10, the interference plus noise signals of one physical resource block on 4 elements in one antenna subarray form a 4 × 12 matrix: $R_{K,j}=\left[\begin{array}{c}{\mathrm{<figure-callout\; id="1"\; label="n"\; filenames="HDA0000089610820000031.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">n</figure-callout>}}_{1,\mathrm{<figure-callout\; id="2"\; label="j\; n"\; filenames="HDA0000089610820000031.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">j</figure-callout>}}& \\ n_{}{}_{2,\mathrm{<figure-callout\; id="3"\; label="j\; n"\; filenames="HDA0000089610820000031.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">j</figure-callout>}}& \\ n_{}{}_{3,\mathrm{<figure-callout\; id="4"\; label="j\; n"\; filenames="HDA0000089610820000042.png,HDA0000089610820000051.png"\; state="\{\{state\}\}">j</figure-callout>}}& \\ n_{}{}_{4,j}\end{array}\right]=\left[\begin{array}{ccccc}{\mathrm{<figure-callout\; id="1"\; label="n"\; filenames="HDA0000089610820000031.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">\; <figure-callout\; id="1"\; label="n"\; filenames="HDA0000089610820000031.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">n</figure-callout>\; </figure-callout>}}_{\mathrm{1,1}}& .& .& .& {\mathrm{<figure-callout\; id="1"\; label="n"\; filenames="HDA0000089610820000031.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">\; <figure-callout\; id="12"\; label="n"\; filenames="HDA0000089610820000071.png"\; state="\{\{state\}\}">n</figure-callout>\; </figure-callout>}}_{\mathrm{1,12}}\\ .& & & & .\\ .& .& .& .& .\\ .& & & & .\\ {\mathrm{<figure-callout\; id="4"\; label="n"\; filenames="HDA0000089610820000042.png,HDA0000089610820000051.png"\; state="\{\{state\}\}">\; <figure-callout\; id="1"\; label="n"\; filenames="HDA0000089610820000031.png,HDA0000089610820000041.png"\; state="\{\{state\}\}">n</figure-callout>\; </figure-callout>}}_{\mathrm{4,1}}& .& .& .& {\mathrm{<figure-callout\; id="4"\; label="n"\; filenames="HDA0000089610820000042.png,HDA0000089610820000051.png"\; state="\{\{state\}\}">\; <figure-callout\; id="12"\; label="n"\; filenames="HDA0000089610820000071.png"\; state="\{\{state\}\}">n</figure-callout>\; </figure-callout>}}_{\mathrm{4,12}}\end{array}\right]$

s903: and calculating the covariance matrix of the interference and noise signals of the physical resource block according to the interference and noise signals.

The concrete formula is as follows:

<math> <mrow> <mi>R</mi> <mo>=</mo> <mi>E</mi> <mo>[</mo> <msub> <mi>n</mi> <mrow> <mi>K</mi> <mo>,</mo> <mi>j</mi> </mrow> </msub> <msup> <msub> <mi>n</mi> <mrow> <mi>K</mi> <mo>,</mo> <mi>j</mi> </mrow> </msub> <mi>H</mi> </msup> <mo>]</mo> <mo>=</mo> <mfrac> <mn>1</mn> <mn>12</mn> </mfrac> <munderover> <mi>&Sigma;</mi> <mrow> <mi>i</mi> <mo>=</mo> <mn>1</mn> </mrow> <mn>12</mn> </munderover> <mfenced open='[' close=']'> <mtable> <mtr> <mtd> <msub> <mi>n</mi> <mn>1,1</mn> </msub> </mtd> <mtd> <mo>.</mo> </mtd> <mtd> <mo>.</mo> </mtd> <mtd> <mo>.</mo> </mtd> <mtd> <msub> <mi>n</mi> <mn>1,12</mn> </msub> </mtd> </mtr> <mtr> <mtd> <mo>.</mo> </mtd> <mtd> </mtd> <mtd> </mtd> <mtd> </mtd> <mtd> <mo>.</mo> </mtd> </mtr> <mtr> <mtd> <mo>.</mo> </mtd> <mtd> <mo>.</mo> </mtd> <mtd> <mo>.</mo> </mtd> <mtd> <mo>.</mo> </mtd> <mtd> <mo>.</mo> </mtd> </mtr> <mtr> <mtd> <mo>.</mo> </mtd> <mtd> </mtd> <mtd> </mtd> <mtd> </mtd> <mtd> <mo>.</mo> </mtd> </mtr> <mtr> <mtd> <msub> <mi>n</mi> <mn>4,1</mn> </msub> </mtd> <mtd> <mo>.</mo> </mtd> <mtd> <mo>.</mo> </mtd> <mtd> <mo>.</mo> </mtd> <mtd> <msub> <mi>n</mi> <mn>4,12</mn> </msub> </mtd> </mtr> </mtable> </mfenced> <msup> <mfenced open='[' close=']'> <mtable> <mtr> <mtd> <msub> <mi>n</mi> <mn>1,1</mn> </msub> </mtd> <mtd> <mo>.</mo> </mtd> <mtd> <mo>.</mo> </mtd> <mtd> <mo>.</mo> </mtd> <mtd> <msub> <mi>n</mi> <mn>1,12</mn> </msub> </mtd> </mtr> <mtr> <mtd> <mo>.</mo> </mtd> <mtd> </mtd> <mtd> </mtd> <mtd> </mtd> <mtd> <mo>.</mo> </mtd> </mtr> <mtr> <mtd> <mo>.</mo> </mtd> <mtd> <mo>.</mo> </mtd> <mtd> <mo>.</mo> </mtd> <mtd> <mo>.</mo> </mtd> <mtd> <mo>.</mo> </mtd> </mtr> <mtr> <mtd> <mo>.</mo> </mtd> <mtd> </mtd> <mtd> </mtd> <mtd> </mtd> <mtd> <mo>.</mo> </mtd> </mtr> <mtr> <mtd> <msub> <mi>n</mi> <mn>4,1</mn> </msub> </mtd> <mtd> <mo>.</mo> </mtd> <mtd> <mo>.</mo> </mtd> <mtd> <mo>.</mo> </mtd> <mtd> <msub> <mi>n</mi> <mn>4,12</mn> </msub> </mtd> </mtr> </mtable> </mfenced> <mi>H</mi> </msup> </mrow> </math>

it can be seen that, compared with the prior art, the matrix inversion dimension in this embodiment is reduced from 8 to 4, the calculation amount is reduced when R is calculated, and Cholesky decomposition in matrix decomposition may be adopted to perform operation on 4 × 4 matrices, thereby avoiding inversion of 8 × 8 matrices and reducing the operation amount of matrix inversion operation.

S904: and calculating a weight matrix according to the covariance matrix and the channel coefficient matrix of the interference and noise signals.

The concrete formula is as follows: w is a_K，j ^H＝h_{K，j_est} ^HR^-1At the same time, w_K，j ^H＝[w_j，1w_j，2w_j，3w_j，4]。

Of course, if the weight matrix w is calculated according to the MRC algorithm_K，j ^HThen, the calculation formula is: w is a_K，j ^H＝h_{K，j_est} ^HAnd the above steps S902 and S903 may be omitted.

S905: according to the weight matrix and h_K，jestAnd calculating the normalized coefficient of each antenna subarray.

The normalized coefficients of the two antenna subarrays are respectively expressed by scale1 and scale2, and the scale1 and the scale2 are calculated in the same way, and the calculation formula is as follows:

scale_i＝w_K，j ^H×h_{K，j_est}＝w_j，1h_{1，j_est}+w_j，2h_{2，j_est}+w_j，3h_{3，j_est}+w_j，4h_{4，j_est}。

it should be noted that w in the above formula_{j_est，1}And h_{1，j_est}Belonging to the same antenna subarray.

S906: and calculating the combined value of the subcarriers of the non-pilot symbols (namely the non-pilot signals) of each antenna subarray according to the weight matrix to obtain the equalization result of the antenna subarray.

The equalization result calculation formula of each antenna subarray is as follows:

y_i＝w_K，j ^H×r＝w_j，1r_1，j+w_j，2r_2，j+w_j，3r_3，j+w_j，4r_4，j。

according to the above formula, the equalization result y of the two antenna subarrays can be obtained by calculation₁And y₂。

S907: and according to the equalization result and the normalization coefficient of the two antenna sub-arrays, carrying out antenna array combination and normalization coefficient adjustment.

Wherein, S907 may specifically include the following steps:

according to the equalization result y of two antenna sub-arrays₁And y₂Obtaining antenna array merging result y through addition operation₀The formula is as follows: y is₀＝y₁+y₂；

According to the normalization coefficients of the two antenna sub-arrays, the normalization coefficients of the antenna array are obtained through addition operation, and the calculation formula is as follows: scale1+ scale 2;

and obtaining a final equalization result by division operation, wherein the calculation formula is as follows: y ═ y₀/scale。

The final equalization result is the combination result of the non-pilot signals. I.e. to recover the non-pilot signal received by the antenna.

In correspondence with the embodiment shown in fig. 9, referring to fig. 11, the present invention further provides a receiving and combining apparatus implementing the method shown in fig. 9, including: a cross polarization antenna 111, an interference and noise signal calculation unit 112, an interference and noise signal covariance calculation unit 113, a channel coefficient matrix calculation unit 114, a weight calculation unit 115 (similar in function to the weight calculation unit 3), a normalization coefficient calculation unit 116 (similar in function to the normalization coefficient calculation unit 4), an antenna subarray equalization calculation unit 117 (similar in function to the antenna subarray equalization calculation unit 5), a two-antenna subarray equalization result combining unit 118 (similar in function to the equalization result combining unit 7), a two-antenna subarray normalization coefficient combining unit 119 (similar in function to the normalization coefficient combining unit 8), a combined value coefficient adjustment unit 120 (similar in function to the adjustment unit 6), an antenna subarray allocation unit (similar in function to the antenna subarray allocation unit 2, not shown in the figures). Wherein:

a cross-polarized antenna 111 for receiving an uplink signal;

and an interference and noise signal calculating unit 112, configured to calculate an interference and noise signal on a pilot symbol subcarrier in the antenna subarray. The interference plus noise signal calculation unit may include a first interference plus noise signal calculation unit and a second interference plus noise signal calculation unit, which are used to calculate the interference plus noise signals in the two antenna sub-arrays respectively;

an interference plus noise signal covariance calculation unit 113 for calculating a covariance matrix of the interference plus noise signals within the antenna sub-array. Similarly, the interference-plus-noise signal covariance calculation unit may also include a first interference-plus-noise signal covariance calculation unit and a second interference-plus-noise signal covariance calculation unit, which are used to calculate covariance matrices of interference-plus-noise signals in the two antenna sub-arrays respectively;

a channel coefficient matrix calculation unit 114 for obtaining h by channel estimation_{K，j_est}. Similarly, the channel coefficient matrix calculation unit may also include a first channel coefficient matrix calculation unit and a second channel coefficient matrix calculation unit for calculating h in the two antenna sub-arrays respectively_{K，j_est}；

And a weight calculation unit 115, configured to calculate a weight matrix required for antenna subarray equalization. Similarly, the weight calculation unit may also include a first weight calculation unit and a second weight calculation unit, which are used to calculate the weights in the two antenna sub-arrays respectively;

and a normalized coefficient calculating unit 116, configured to calculate a normalized coefficient of the antenna subarray. Similarly, the normalization coefficient calculation unit may also include a first normalization coefficient calculation unit and a second normalization coefficient calculation unit, which are used to calculate the normalization coefficients in the two antenna sub-arrays respectively;

and an antenna sub-array equalization calculation unit 117, configured to perform equalization in the antenna sub-array and intra-sub-array combining to obtain an equalization result of the antenna sub-array.

The two-antenna subarray equalization result merging unit 118 is used for summing the two-antenna subarray equalization results;

the two-antenna subarray normalization coefficient combining unit 119 is used for summing normalization coefficients of the two-antenna subarrays;

a merging value coefficient adjusting unit 120, configured to perform normalization coefficient adjustment on the merging value of the last data subcarrier, so as to obtain a merging result of the non-pilot signal.

How the interference plus noise signal calculating unit 112 obtains the interference plus noise signal can be referred to the above description, and is not described herein again.

The weight calculation unit 115 may calculate the weight according to the IRC and MRC algorithms, and for related contents, please refer to the foregoing description, which is not described herein again.

The embodiments in the present description are described in a progressive manner, each embodiment focuses on differences from other embodiments, and the same and similar parts among the embodiments are referred to each other. The device disclosed by the embodiment corresponds to the method disclosed by the embodiment, so that the description is simple, and the relevant points can be referred to the method part for description.

The steps of a method or algorithm described in connection with the embodiments disclosed herein may be embodied directly in hardware, in a software module executed by a processor, or in a combination of the two. A software module may reside in Random Access Memory (RAM), memory, Read Only Memory (ROM), electrically programmable ROM, electrically erasable programmable ROM, registers, hard disk, a removable disk, a CD-ROM, or any other form of storage medium known in the art.

The previous description of the disclosed embodiments is provided to enable any person skilled in the art to make or use the present invention. Various modifications to these embodiments will be readily apparent to those skilled in the art, and the generic principles defined herein may be applied to other embodiments without departing from the spirit or scope of the invention. Thus, the present invention is not intended to be limited to the embodiments shown herein but is to be accorded the widest scope consistent with the principles and novel features disclosed herein.

Claims (8)

1. A cross-polarized antenna system receive combining method, comprising:

dividing cross polarization antennas in the cross polarization antenna system into antenna sub-arrays according to polarization directions, wherein each antenna sub-array comprises array elements with the same polarization directions, and the cross polarization antennas are used for receiving uplink signals;

respectively carrying out weight matrix calculation on each antenna subarray, and carrying out normalization coefficient calculation on the corresponding antenna subarrays by using the weight matrix;

carrying out channel equalization on the non-pilot signals received by the corresponding antenna subarrays by using the weight matrix to obtain an equalization result;

according to the equalization result and the normalization coefficient of the antenna subarray, carrying out antenna array combination and normalization coefficient adjustment to obtain a combination result of non-pilot signals;

the specific implementation of the antenna array combination and the normalization coefficient adjustment according to the equalization result and the normalization coefficient of the antenna subarray to obtain the combination result of the non-pilot signals comprises the following steps:

summing the equalization results of each antenna subarray to obtain a total equalization result;

summing the normalization coefficients of each antenna subarray to obtain a total normalization coefficient;

and dividing the total equalization result by the total normalization coefficient to obtain a combination result of the non-pilot signals.

2. The method of claim 1,

the specific implementation of utilizing the weight matrix to calculate the normalization coefficient of the corresponding antenna subarray comprises:

and multiplying the conjugate transpose of the weight matrix by a channel coefficient matrix obtained through channel estimation to obtain a normalized coefficient.

3. The method of claim 1, wherein the specific implementation of the weight matrix calculation comprises:

taking the conjugate transpose of the channel coefficient matrix obtained by channel estimation as the conjugate transpose of the weight matrix; or,

multiplying the conjugate transpose of the channel coefficient matrix obtained by channel estimation by the inverse matrix of the covariance matrix of the interference-plus-noise signal of the corresponding antenna subarray to obtain the conjugate transpose of the weight matrix;

the covariance matrix of the interference and noise signals is obtained by calculating the statistical average after multiplying the interference and noise signal matrix by the conjugate transpose of the interference and noise signal matrix.

4. The method of claim 3, wherein the interference plus noise signal matrix is obtained by:

after the pilot signal received by the antenna subarray is used as a reference signal to perform complex correlation with a local reference signal, a channel coefficient matrix containing interference and noise signals is obtained;

and subtracting the channel coefficient matrix containing the interference and noise signals from the channel coefficient matrix obtained through channel estimation to obtain the interference and noise signal matrix.

5. The method according to any of claims 1-4, wherein the performing channel equalization on the non-pilot signals received by the corresponding antenna subarrays using the weight matrix to obtain an equalization result comprises:

and multiplying the conjugate transpose of the weight matrix by a non-pilot frequency subcarrier data matrix received by the antenna subarray to obtain the equalization result, wherein the non-pilot frequency subcarrier data matrix forms the non-pilot frequency signal.

6. A cross-polarized antenna system receive combining apparatus, comprising:

a cross-polarized antenna for receiving an uplink signal;

the antenna subarray distribution unit is used for dividing the cross polarization antenna into antenna subarrays according to the polarization direction, and each antenna subarray comprises array elements with the same polarization direction;

the weight calculation unit is used for respectively calculating a weight matrix of each antenna subarray;

the normalization coefficient calculation unit is used for calculating the normalization coefficient of the corresponding antenna subarrays by utilizing the weight matrix calculated by the weight calculation unit;

the antenna subarray equalization calculation unit is used for carrying out channel equalization on the non-pilot signals received by the corresponding antenna subarrays by utilizing the weight matrix to obtain an equalization result;

the adjusting unit is used for carrying out antenna array combination and normalization coefficient adjustment according to the equalization result and the normalization coefficient of the antenna subarray to obtain a combination result of the non-pilot signals;

the adjusting unit includes:

the equalization result merging unit is used for summing the equalization results of the antenna subarrays to obtain a total equalization result;

the normalization coefficient combining unit is used for summing the normalization coefficients of the antenna subarrays to obtain a total normalization coefficient;

and the division calculating unit is used for dividing the total equalization result by the total normalization coefficient to obtain a combination result of the non-pilot signals.

7. The apparatus of claim 6, wherein the specific implementation of the weight matrix calculation comprises:

taking the conjugate transpose of the channel coefficient matrix obtained by channel estimation as the conjugate transpose of the weight matrix; or,

multiplying the conjugate transpose of the channel coefficient matrix obtained by channel estimation by the inverse matrix of the covariance matrix of the interference-plus-noise signal of the corresponding antenna subarray to obtain the conjugate transpose of the weight matrix;

the covariance matrix of the interference and noise signals is obtained by calculating the statistical average after multiplying the interference and noise signal matrix by the conjugate transpose of the interference and noise signal matrix.

8. The apparatus of claim 7, further comprising an interference plus noise signal calculation unit and a channel coefficient matrix calculation unit, wherein:

the channel coefficient matrix calculation unit is used for performing complex correlation on a pilot signal received by the antenna subarray as a reference signal and a local reference signal to obtain a channel coefficient matrix containing interference and noise signals;

and the interference and noise signal calculation unit is used for subtracting the channel coefficient matrix containing the interference and noise signals from the channel coefficient matrix obtained through channel estimation to obtain the interference and noise signal matrix.

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